Product Order Technical Tools & Support & Folder Now Documents Software Community UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 UCC280x Low-Power BiCMOS Current-Mode PWM Controllers 1 Features 3 Description • 100-μAtypicalstartingsupplycurrent The UCC280x family of high-speed, low-power 1 integrated circuits contain all of the control and drive • 500-μAtypicaloperatingsupplycurrent components required for off-line and DC-to-DC fixed • Operationupto1MHz frequency current-mode switching mode power • Internalsoftstart supplieswithminimalpartscount. • Internalfaultsoftstart These devices have the same pin configuration as • Internalleading-edgeblankingofthecurrent the UCx84x family, and also offer the added features of internal full-cycle soft start and internal leading- sensesignal edgeblankingofthecurrent-senseinput. • 1-Atotem-poleoutput • 70-nstypicalresponsefromcurrent-sensetogate DeviceInformation(1) driveoutput PARTNUMBER PACKAGE BODYSIZE(NOM) • 1.5%tolerancevoltagereference UCC2800, • SamepinoutasUC3842andUC3842A UCC2801, UCC2802, SOIC(8) 3.91mm×4.90mm UCC2803, 2 Applications UCC2804, UCC2805 • Switchmodepowersupplies(SMPS) (1) For all available packages, see the orderable addendum at • DC-to-DCconverters theendofthedatasheet. • Powermodules • AutomotivePSU • Battery-operatedPSU SimplifiedApplicationDiagram Vin Vout UCC2803 7 VCC OUT 6 8 REF CS 3 FB 2 C C out in 4 RC GND COMP 5 1 Copyright © 2016, Texas Instruments Incorporated 1 An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications, intellectualpropertymattersandotherimportantdisclaimers.PRODUCTIONDATA.

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com Table of Contents 1 Features.................................................................. 1 9.3 FeatureDescription.................................................11 2 Applications........................................................... 1 9.4 DeviceFunctionalModes.......................................23 3 Description............................................................. 1 10 ApplicationandImplementation........................ 25 4 RevisionHistory..................................................... 2 10.1 ApplicationInformation..........................................25 10.2 TypicalApplication ...............................................25 5 Description(continued)......................................... 3 11 PowerSupplyRecommendations..................... 34 6 DeviceComparisonTable..................................... 3 12 Layout................................................................... 34 7 PinConfigurationandFunctions......................... 4 12.1 LayoutGuidelines ................................................34 8 Specifications......................................................... 6 12.2 LayoutExample....................................................36 8.1 AbsoluteMaximumRatings......................................6 13 DeviceandDocumentationSupport................. 37 8.2 ESDRatings..............................................................6 13.1 CommunityResources..........................................37 8.3 RecommendedOperatingConditions.......................6 13.2 Trademarks...........................................................37 8.4 ThermalInformation .................................................7 13.3 RelatedLinks........................................................37 8.5 ElectricalCharacteristics...........................................7 13.4 ElectrostaticDischargeCaution............................37 8.6 TypicalCharacteristics..............................................9 13.5 Glossary................................................................37 9 DetailedDescription............................................ 11 14 Mechanical,Packaging,andOrderable 9.1 Overview.................................................................11 Information........................................................... 38 9.2 FunctionalBlockDiagram.......................................11 4 Revision History NOTE:Pagenumbersforpreviousrevisionsmaydifferfrompagenumbersinthecurrentversion. ChangesfromRevisionF(June,2016)toRevisionG Page • AddedPowerSupplysectiontoreflectpowerupofthedevice............................................................................................. 6 ChangesfromRevisionE(June2016)toRevisionF Page • AddedMaximumJunctionTemperature................................................................................................................................ 6 • AddedRecommendedjunctiontemperaturerange............................................................................................................... 6 ChangesfromRevisionD(August2010)toRevisionE Page • AddedESDRatingstable,FeatureDescriptionsection,DeviceFunctionalModes,ApplicationandImplementation section,PowerSupplyRecommendationssection,Layoutsection,DeviceandDocumentationSupportsection,and Mechanical,Packaging,andOrderableInformationsection.................................................................................................. 1 ChangesfromRevisionA(September2000)toRevisionB Page • UpdatedAbsMaxTabletoread:AnalogInputs(FB,CS,RC,COMP)...–0.3Vtothelesserof6.3VorVCC+0.3V From:AnalogInputs(FB,CS)...–0.3Vto6.3V...................................................................................................................... 6 2 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 5 Description (continued) The UCC280x family offers a variety of package options, temperature range options, choice of maximum duty cycle, and choice of critical voltage levels. Lower reference parts such as the UCC2803 and UCC2805 fit best into battery-operated systems, while the higher reference and higher UVLO hysteresis of the UCC2802 and UCC2804maketheseidealchoicesforuseinoff-linepowersupplies. TheUCC280xseriesisspecifiedforoperationfrom–40°Cto125°C. 6 Device Comparison Table DeviceComparisonTable PARTNUMBER MAXIMUMDUTYCYCLE REFERENCEVOLTAGE TURNONTHRESHOLD TURNOFFTHRESHOLD UCC2800 100% 5V 7.2V 6.9V UCC2801 50% 5V 9.4V 7.4V UCC2802 100% 5V 12.5V 8.3V UCC2803 100% 4V 4.1V 3.6V UCC2804 50% 5V 12.5V 8.3V UCC2805 50% 4V 4.1V 3.6V TemperatureandPackageSelectionTable TEMPERATURERANGE AVAILABLEPACKAGES UCC280x –40°Cto125°C D Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 3 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com 7 Pin Configuration and Functions UCC280xDPackage 8-PinSOIC TopView COMP 1 8 REF FB 2 7 VCC CS 3 6 OUT RC 4 5 GND PinFunctions PIN I/O DESCRIPTION NAME SOIC COMPistheoutputoftheerroramplifierandtheinputofthePWMcomparator. TheerroramplifierintheUCC280xfamilyisatrue,lowoutputimpedance,2-MHz operational amplifier. As such, the COMP terminal can both source and sink COMP 1 O current. However, the error amplifier is internally current-limited, so the user can commandzerodutycyclebyexternallyforcingCOMPtoGND. TheUCC280xfamilyfeaturesbuilt-infull-cyclesoftstart.Softstartisimplemented asaclamponthemaximumCOMPvoltage. CS is the input to the current sense comparators. The UCC280x family has two different current sense comparators: the PWM comparator and an overcurrent comparator. TheUCC280xfamilycontainsdigitalcurrentsensefiltering,whichdisconnectsthe CS terminal from the current sense comparator during the 100-ns interval immediately following the rising edge of the OUT pin. This digital filtering, also CS 3 I called leading-edge blanking, means that in most applications, no analog filtering (RC filter) is required on CS. Compared to an external RC filter technique, the leading-edgeblankingprovidesa smaller effective CStoOUTpropagationdelay. Note, however, that the minimum non-zero On-time of the OUT signal is directly affectedbytheleading-edge-blankingandtheCStoOUTpropagationdelay. The overcurrent comparator is onlyintendedfor faultsensing, and exceeding the overcurrentthresholdcausesasoft-startcycle. FBistheinvertinginputoftheerroramplifier.Forbeststability,keepFBlead FB 2 I lengthasshortaspossibleandFBstraycapacitanceassmallaspossible. GND 5 — GNDisreferencegroundandpowergroundforallfunctionsonthispart. NC — — Noconnectionpins OUT is the output of a high-current power driver capable of driving the gate of a powerMOSFETwithpeakcurrentsexceeding±750mA.OUTisactivelyheldlow whenVCCisbelowtheUVLOthreshold. OUT 6 O Thehigh-currentpowerdriverconsistsofFEToutputdevices,whichcanswitchall of the way to GND and all of the way to V . The output stage also provides a CC verylowimpedancetoovershootandundershoot.Thismeansthatinmanycases, externalschottkyclampdiodesarenotrequired. PWRGND — — PowergroundoftheIC 4 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 PinFunctions(continued) PIN I/O DESCRIPTION NAME SOIC RCis theoscillatortiming pin. Forfixed frequencyoperation,settiming capacitor charging current by connecting a resistor from REF to RC. Set frequency by connecting a timing capacitor from RC to GND. For best performance, keep the timing capacitor lead to GND as short and direct as possible. If possible, use separategroundtracesforthetimingcapacitorandallotherfunctions. Thefrequencyofoscillationcanbeestimatedwiththefollowingequations: 1.5 = f R´C (1) 1.0 RC 4 I = f R´C where • frequencyisinHz • resistanceisinΩ • capacitanceisinfarads (2) Therecommendedrangeoftimingresistorsisbetween10kand200k,andtiming capacitoris100pFto1000pF.Neveruseatimingresistorlessthan10k. REF is the voltage reference for the error amplifier, and also for many other functions on the IC. REF is also used as the logic power supply for high-speed switchinglogicontheIC. WhenVCCisgreaterthan1VandlessthantheUVLOthreshold,REFispulledto ground through a 5-kΩ resistor. This means that REF can be used as a logic REF 8 O output indicating power system status. It is important for reference stability that REFisbypassedtoGNDwithaceramiccapacitorasclosetothepinaspossible. Anelectrolyticcapacitormayalsobeusedinaddition totheceramiccapacitor.A minimum of 0.1-μF ceramic is required. Additional REF bypassing is required for externalloadsgreaterthan2.5mAonthereference. To prevent noise problems with high speed switching transients, bypass REF to groundwithaceramiccapacitorveryclosetotheICpackage. VCC is the power input connection for this device. In normal operation, VCC is powered through a current limiting resistor. Although quiescent VCC current is very low, total supply current is higher depending on OUT current. Total VCC current is the sum of quiescent VCC current and the average OUT current. Knowing the operating frequency and the MOSFET gate charge (Q ), average g OUTcurrentcanbecalculatedfrom: VCC 7 I I =Q ´ f OUT g (3) To prevent noise problems, bypass VCC to GND with a ceramic capacitor as close to the VCC pin as possible. An electrolytic capacitor may also be used in addition to the ceramic capacitor. There must be a minimum of 1 µF in parallel witha0.1-µFceramiccapacitorfromVCCtogroundplacedclosetothedevice. Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 5 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com 8 Specifications 8.1 Absolute Maximum Ratings overoperatingfree-airtemperaturerange(unlessotherwisenoted)(1)(2) MIN MAX UNIT VCCvoltage(3) 12 V VCCcurrent(3) 30 mA OUTcurrent ±1 A OUTenergy(capacitiveload) 20 µJ Analoginputs(FB,CS,RC,COMP) –0.3 6.3orVCC+0.3(4) V NorJpackage 1 PowerdissipationatT <25°C Dpackage 0.65 W A Lpackage 1.375 Leadtemperature,soldering(10s) 300 °C StorageTemperature,T –65 150 °C stg JunctionTemperature,T -55 150 °C J (1) AllvoltagesarewithrespecttoGND.Allcurrentsarepositiveintothespecifiedterminal. (2) StressesbeyondthoselistedunderAbsoluteMaximumRatingsmaycausepermanentdamagetothedevice.Thesearestressratings only,whichdonotimplyfunctionaloperationofthedeviceattheseoranyotherconditionsbeyondthoseindicatedunderRecommended OperatingConditions.Exposuretoabsolute-maximum-ratedconditionsforextendedperiodsmayaffectdevicereliability. (3) InnormaloperationVccispoweredthroughacurrentlimitresistor.TheresistormustbesizedsothattheVCCvoltageunderall operatingconditionsisbelow12Vbutabovetheturnoffthreshold.Absolutemaximumof12VapplieswhenVCCisdrivenfromalow impedancesourcesuchthatICCdoesnotexceed30mA.FailuretolimitVCCandICCtotheselimitsmayresultinpermanentdamage ofthedevice.ThisisfurtherdiscussedinthePowerSupplyRecommendations. (4) Returntheminimum(lesser)valueofthetwo. 8.2 ESD Ratings VALUE UNIT DPACKAGES Human-bodymodel(HBM),perAECQ100-002(1) ±2500 V Electrostaticdischarge V (ESD) Charged-devicemodel(CDM),perAECQ100-011(1) ±1500 (1) AECQ100-002indicatesthatHBMstressingshallbeinaccordancewiththeANSI/ESDA/JEDECJS-001specifications. 8.3 Recommended Operating Conditions overoperatingfree-airtemperaturerange(unlessotherwisenoted) MIN MAX UNIT V VCCbiassupplyvoltagefromlowimpedancesource 11 V VCC V ,V , FB CS Voltageonanalogpins –0.1 6orV V V ,V VCC RC COMP V Gatedriveroutputvoltage –0.1 V V OUT VCC I Supplybiascurrent 25 mA VCC I AverageOUTpincurrent 20 mA OUT I REFpinoutputcurrent 5 mA REF f Oscillatorfrequency 1 MHz OSC T Operatingfree-airtemperature –55 125 °C A T JunctionTemperature -55 125 °C J 6 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 8.4 Thermal Information UCC280x THERMALMETRIC(1) D(SOIC) UNIT 8PINS R Junction-to-ambientthermalresistance 107.5 °C/W θJA R Junction-to-case(top)thermalresistance 49.3 °C/W θJC(top) R Junction-to-boardthermalresistance 48.7 °C/W θJB ψ Junction-to-topcharacterizationparameter 6.6 °C/W JT ψ Junction-to-boardcharacterizationparameter 48 °C/W JB R Junction-to-case(bottom)thermalresistance — °C/W θJC(bot) (1) Formoreinformationabouttraditionalandnewthermalmetrics,seetheSemiconductorandICPackageThermalMetricsapplication report. 8.5 Electrical Characteristics –40°C≤T ≤125°CforUCC280x.V =10V(1),RT=100kfromREFtoRC,CT=330pFfromRCtoGND,0.1-uF A CC capacitorfromV toGND,0.1-uFcapacitorfromV toGND,andT =T (unlessotherwisenoted). CC REF A J PARAMETER TESTCONDITIONS MIN TYP MAX UNIT REFERENCE TJ=25°C,I=0.2mA,UCC2800,UCC2801,UCC2802,and 4.925 5 5.075 Outputvoltage UCC2804 V TJ=25°C,I=0.2mA,UCC2803andUCC2805 3.94 4 4.06 Loadregulation 0.2mA<I<5mA UCC280x 10 30 mV TJ=25°C,VCC=10Vtoclamp(IVCC=25mA) 1.9 Lineregulation TJ=–40°Cto125°C,VCC=10Vto UCC280x 2.5 mV/V clamp(IVCC=25mA) UCC2800,UCC2801,UCC2802,andUCC2804(2) 4.88 5 5.1 Totalvariation V UCC2803andUCC2805(2) 3.9 4 4.08 Outputnoisevoltage 10Hz≤f≤10kHz,TJ=25°C(3) 130 µV Longtermstability TA=125°C,1000hours(3) 5 mV Outputshortcircuit –5 –35 mA OSCILLATOR UCC2800,UCC2801,UCC2802,UCC2804(4) 40 46 52 Oscillatorfrequency kHz UCC2803andUCC2805(4) 26 31 36 Temperaturestability(3) 2.5 % Amplitudepeak-to-peak 2.25 2.4 2.55 V Oscillatorpeakvoltage 2.45 V ERRORAMPLIFIER COMP=2.5V,UCC2800,UCC2801,UCC2802,andUCC2804 2.44 2.5 2.56 Inputvoltage V COMP=2V,UCC2803andUCC2805 1.95 2 2.05 Inputbiascurrent –1 1 µA Openloopvoltagegain 60 80 dB COMPsinkcurrent FB=2.7V,COMP=1.1V UCC280x 0.3 3.5 mA COMPsourcecurrent FB=1.8V,COMP=REF–1.2V –0.2 –0.5 –0.8 mA Gainbandwidthproduct(3) 2 MHz (1) AdjustVCCabovethestartthresholdbeforesettingat10V. (2) Totalvariationincludestemperaturestabilityandloadregulation. (3) Ensuredbydesign.Not100%testedinproduction. (4) OscillatorfrequencyfortheUCCx800,UCC2802,andUCC2803istheoutputfrequency.OscillatorfrequencyfortheUCC2801, UCC2804,andUCC2805istwicetheoutputfrequency. Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 7 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com Electrical Characteristics (continued) –40°C≤T ≤125°CforUCC280x.V =10V(1),RT=100kfromREFtoRC,CT=330pFfromRCtoGND,0.1-uF A CC capacitorfromV toGND,0.1-uFcapacitorfromV toGND,andT =T (unlessotherwisenoted). CC REF A J PARAMETER TESTCONDITIONS MIN TYP MAX UNIT PWM UCC2800,UCC2802,andUCC2803 97 99 100 Maximumdutycycle % UCC2801,UCC2804,andUCC2805 48 49 50 CURRENTSENSE Gain(5) 1.1 1.65 1.8 V/V Maximuminputsignal COMP=5V(6) 0.9 1 1.1 V Inputbiascurrent –200 200 nA CSblanktime 50 100 150 ns Overcurrentthreshold 1.42 1.55 1.68 V COMPtoCSoffset CS=0V 0.45 0.9 1.35 V OUTPUT I=20mA,allparts 0.1 0.4 I=200mA,allparts 0.35 0.9 OUTlowlevel V I=50mA,VCC=5V,UCC2803andUCC2805 0.15 0.4 I=20mA,VCC=0V,allparts 0.7 1.2 I=20mA,allparts 0.15 0.4 OUThighVSAT(VCC-OUT) I=200mA,allparts 1 1.9 V I=50mA,VCC=5V,UCC2803andUCC2805 0.4 0.9 Risetime CL=1nF 41 70 ns Falltime CL=1nF 44 75 ns UNDERVOLTAGELOCKOUT UCC2800 6.6 7.2 7.8 UCC2801 8.6 9.4 10.2 Startthreshold(7) V UCC2802andUCC2804 11.5 12.5 13.5 UCC2803andUCC2805 3.7 4.1 4.5 UCC2800 6.3 6.9 7.5 UCC2801 6.8 7.4 8 Stopthreshold(7) V UCC2802andUCC2804 7.6 8.3 9 UCC2803andUCC2805 3.2 3.6 4 UCC2800 0.12 0.3 0.48 UCC2801 1.6 2 2.4 Starttostophysteresis V UCC2802andUCC2804 3.5 4.2 5.1 UCC2803andUCC2805 0.2 0.5 0.8 SOFTSTART COMPrisetime FB=1.8V,risefrom0.5VtoREF–1V 4 10 ms OVERALL Start-upcurrent VCC<startthreshold 0.1 0.2 mA Operatingsupplycurrent FB=0V,CS=0V 0.5 1 mA VCCinternalZenervoltage ICC=10mA(7)(8) 12 13.5 15 V VCCinternalZenervoltageminus UCC2802andUCC2804(7) 0.5 1 V startthresholdvoltage (5) Gainisdefinedby:A=ΔV /ΔV .0≤V ≤0.8V COMP CS CS (6) ParametermeasuredattrippointoflatchwithPin2at0V. (7) Startthreshold,stopthreshold,andZenershuntthresholdstrackoneanother. (8) Thedeviceisfullyoperatinginclampmode,astheforcingcurrentishigherthanthenormaloperatingsupplycurrent. 8 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 8.6 Typical Characteristics 4.00 3.98 3.96 3.94 V) 3.92 ( F E R 3.90 V 3.88 3.86 3.84 3.82 4 4.2 4.4 4.6 4.8 5 5.2 5.4 5.6 5.8 6 VCC(V) Figure1.ErrorAmplifierGainandPhaseResponse Figure2.UCC2803andUCC2805V vsV , REF CC I =0.5mA LOAD 1000 1000 z) z) H H k k ( ( q. q. e e Oscillator Fr 100 132030000pppFFF Oscillator Fr 100 321300000pppFFF 10 1nF 10 1nF 10 100 1000 10 100 1000 RT(k ) RT(k ) Figure3.UCC2800,UCC2801,UCC2802,andUCC2804 Figure4.UCC2803andUCC2805OscillatorFrequency OscillatorFrequencyvsRTandCT vsRTandCT 100 50 99.5 49.5 %) 99 %) e ( 98.5 e ( 49 mum Duty Cycl 9799.578 CT= 33C0TpF= 200pCFT= 100pF mum Duty Cycl 484.85 CT= 330pCFT= 200CpTF= 100pF axi 96.5 axi 47.5 M M 96 47 95.5 95 46.5 10 100 1000 10 100 1000 Oscillator Frequency (kHz) Oscillator Frequency (kHz) Figure5.UCC2800,UCC2802,andUCC2803MaximumDuty Figure6.UCC2801,UCC2804,andUCC2805MaximumDuty CyclevsOscillatorFrequency CyclevsOscillatorFrequency Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 9 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com Typical Characteristics (continued) 16 8 14 7 (mA) 11802 VCC =V C1 C0 V=, 18nV,F 1nF (mA) 456 VCC V= C 1 C 0 V=, 81Vn, F1nF C C IC 246 VC VC C=C 1=0 V8,V N, No oL oLaodad IC 123 VC VC C =C 1=0 V8,V N, No oL oLaodad 0 0 0 100 200 300 400 500 600 700 800 900 1000 0 100 200 300 400 500 600 700 800 900 1000 Oscillator Frequency (kHz) Oscillator Frequency (kHz) Figure7.UCC2800I vsOscillatorFrequency Figure8.UCC2805I vsOscillatorFrequency CC CC 1.1 s) 1.0 olt V et ( 0.9 s Off CS 0.8 Slope = 1.8mV/°C o Pt 0.7 M O C 0.6 0 -55-50 -25 0 25 50 75 100 125 Temperature (°C) Figure10.COMPtoCSOffsetvsTemperature,CS=0V Figure9.DeadTimevsC ,R =100k T T 10 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 9 Detailed Description 9.1 Overview The UCC280x family of high-speed, low-power integrated circuits contain all of the control and drive components required for off-line and DC-to-DC fixed-frequency, current-mode switching mode power supplies with minimal partscount. These devices have the same pin configuration as the UCx84x family, and also offer the added features of internalfull-cyclesoftstartandinternalleading-edgeblankingofthecurrent-senseinput. 9.2 Functional Block Diagram FB COMP CS 2 1 3 VCC 7 Leading Edge UCCx801 Blanking UCCx804 1.5V UCCx805 only VCC Over-Current REF/2 OK T Q S Q OUT R 0.65R Oscillator S Q 6 R 4V Voltage S Q PWM Reference Latch REF R 13.5V OK 0.5V Logic Power R 1V Full Cycle Soft Start j=4ms GND 5 8 4 REF RC Copyright © 2016, Texas Instruments Incorporated 9.3 Feature Description The UCC280x family offers numerous advantages that allow the power supply design engineer to meet these challengingrequirements. Featuresinclude: • Bi-CMOSprocess • Lowstartingsupplycurrent:typically100μA • Lowoperatingsupplycurrent:typically500μA • PinoutcompatiblewithUC3842andUC3842Afamilies • 5-Voperation(UCC2803andUCC2805) • Leadingedgeblankingofcurrentsensesignal • On-chipsoftstart • Internalfullcyclerestartdelay • 1.5%voltagereference • Upto1-MHzoscillator • Lowself-biasingoutputduringUVLO • Veryfewexternalcomponentsrequired • 70-nsresponsefromcurrentsensetooutput • Availableinsurface-mountorPDIPpackage Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 11 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com Feature Description (continued) The UCC280x family of devices are pinout compatible with the UCx84x and UCx84xA families. However, they are not plug-in compatible. In general, the UCC280x requires fewer external components and consumes less operatingcurrent. 9.3.1 DetailedPinDescription 9.3.1.1 COMP Unlike other devices, the error amplifier in the UCC280x family is a true, low output impedance, 2-MHz operational amplifier. As such, the COMP terminal can both source and sink current. However, the error amplifier isinternallycurrent-limited,sothatonecancommandzerodutycyclebyexternallyforcingCOMPtoGND. The UCC280x has a true low output impedance error amplifier which both sources and sinks current. The error amplifierassociatedwiththeUC3842familyisanopencollectorinparallelwithacurrentsource. The UCC280x has power-up soft start and fault soft start built on-chip with a fixed COMP rise time to 5 V in 4ms.Therefore,noexternalsoft-startcircuitryisrequired,saving1resistor,1capacitor,and1PNPtransistor. 9.3.1.2 FB FB is the inverting input of the error amplifier. For best stability, keep FB lead length as short as possible and FB straycapacitanceassmallaspossible. The UCC280x features a 2-MHz bandwidth error amplifier versus 1 MHz on the UC3842 family. Feedback techniquesareidenticaltotheUC3842family. 9.3.1.3 CS CS is the PWM comparator and an overcurrent comparator. The UCC280x family contains digital current sense filtering, which disconnects the CS terminal from the current sense comparator during the 100-ns interval immediately following the rising edge of the OUT pin. This digital filtering, also called leading-edge blanking, means that in most applications, no analog filtering (RC filter) is required on CS. Compared to an external RC filter technique, the leading-edge blanking provides a smaller effective CS to OUT propagation delay. Note, however, that the minimum non-zero on-time of the OUT signal is directly affected by the leading-edge-blanking and the CS to OUT propagation delay. The overcurrent comparator is only intended for fault sensing, and exceedingtheovercurrentthresholdcausesasoft-startcycle. The UCC280x current sense is significantly different from its predecessor. The UC3842 family current sense input connects to only the PWM comparator. The UCC280x current sense input connects to two comparators: the PWM comparator and the overcurrent comparator. Internal leading edge blanking masks the first 100 ns of the current sense signal. This may eliminate the requirement for an RC current sense filter and prevent false triggering due to leading edge noises. Connect CS directly to MOSFET source current sense resistor. The gain ofthecurrentsenseamplifieronthe UCC280x family is typically 1.65 V/V versus typically 3 V/V with the UC3842 family. 9.3.1.4 RC RC is the oscillator timing pin. For fixed frequency operation, set timing capacitor charging current by connecting a resistor from REF to RC. Set frequency by connecting timing capacitor from RC to GND. For the best performance, keep the timing capacitor lead to GND as short and direct as possible. If possible, use separate groundtracesforthetimingcapacitorandallotherfunctions. The UCC280x’s oscillator allows for operation to 1 MHz versus 500 kHz with the UC3842 family. Both devices make use of an external resistor to set the charging current for the capacitor, which determines the oscillator frequency.FortheUCC2802andUCC2804,useEquation4. 1.5 = f R´C (4) FortheUCC2803andUCC2805,useEquation5. 1.0 = f R´C (5) 12 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 Feature Description (continued) Inthesetwoequations,switchingfrequency(f)isinHz,RisinΩ,andCisinfarads. The two equations are different due to different reference voltages. The recommended range of timing resistor values is between 10 kΩ and 200 kΩ; the recommended range of timing capacitor values is between 100 pF and 1000 pF. The peak-to-peak amplitude of the oscillator waveform is 2.45 V versus 1.7 V in UC3842 family. For best performance, keep the timing capacitor lead to GND as short as possible. TI recommends separate ground traces for the timing capacitor and all other pins. The maximum duty cycle for the UCC2802 and UCC2803 is approximately 99%; the maximum duty cycle for the UCC2803 and UCC2804 is approximately 49%. The duty cycle cannot be easily modified by adjusting R and C , unlike the UC3842A family. The maximum duty cycle T T limitissetbytheratiooftheexternaloscillatorchargingresistorR and the internal oscillator discharge transistor T on-resistance, like the UC3842. However, maximum duty cycle limits less than 90% (for the UCC2802 and UCC2803) and less than 45% (for the UCC2804 and UCC2805) can not reliably be set in this manner. For better controlofmaximumdutycycle,considerusingtheUCCx807. 9.3.1.5 GND GNDpinisthesignal and power returning ground. TI recommends separating the signal return path and the high currentgatedriverpathsothatthesignalisnotaffectedbytheswitchingcurrent. 9.3.1.6 OUT OUT is the output of a high-current power driver capable of driving the gate of a power MOSFET with peak currents exceeding 750 mA. OUT is actively held low when VCC is below the UVLO threshold. The high-current power driver consists of FET output devices, which can switch all of the way to GND and all of the way to VCC. The output stage also provides a low impedance to overshoot and undershoot. This means that in many cases, externalSchottkyclampdiodesarenotrequired. The output of the UCC280x is a CMOS output versus a Bipolar output on the UC3842 family. Peak output current remains the same ±1 A. The CMOS output provides very smooth rising and falling waveforms, with virtually no overshoot or undershoot. Additionally, the CMOS output provides a low resistance to the supply in response to overshoot, and a low resistance to ground in response to undershoot. Because of this, Schottky diodes may not be necessary on the output. Furthermore, the UCC2802 has a self-biasing, active low output duringUVLO.Thisfeatureeliminatesthegatetosource bleederresistorassociatedwiththeMOSFET gate drive. Finally, no MOSFET gate voltage clamp is necessary with the UCC280x as the on-chip Zener diode automaticallyclampstheoutputtoVCC. 9.3.1.7 VCC VCC is the power input connection for this device. In normal operation, VCC is powered through a current limiting resistor. Although quiescent VCC current is very low, total supply current is higher, depending on the OUT current. Total VCC current is the sum of quiescent VCC current and the average OUT current. Knowing the operating frequency and the MOSFET gate charge (Qg), average OUT current can be calculated from Equation6. I =Q ´ f OUT g (6) The UCC280x has a lower VCC (supply voltage) clamp of 13.5 V typical versus 30 V on the UC3842. For applications that require a higher VCC voltage, a resistor must be placed in series with VCC to increase the sourceimpedance.ThemaximumvalueofthisresistoriscalculatedwithEquation7. V -V IN:min; VCC:max; R = max I +Q ×f VCC g (7) In Equation 7, V (min) is the minimum voltage that is used to supply VCC, V (max) is the maximum VCC IN VCC clamp voltage and I is the IC supply current without considering the gate driver current and Q is the external VCC g powerMOSFETgatechargeandfistheswitchingfrequency. Additionally, the UCC280x has an on-chip Zener diode to regulate VCC to 13.5 V. The turnon and turnoff thresholds for the UCC280x family are significantly different: 12.5 V and 8 V for the UCC2802 and UCC2804; 4.1 V and 3.6 V for the UCC2803 and UCC2805. 5-V PWM operation is now possible. To ensure against noise related problems, filter VCC with an electrolytic and bypass with a ceramic capacitor to ground. Keep the capacitorsclosetotheICpins. Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 13 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com Feature Description (continued) 9.3.1.8 Pin8(REF) REFisthe voltage reference for the error amplifier and also for many other functions on the IC. REF is also used as the logic power supply for high-speed switching logic on the IC. When VCC is greater than 1 V and less than the UVLO threshold, REF is pulled to ground through a 5-kΩ resistor. This means that REF can be used as a logic output indicating power system status. It is important for reference stability that REF is bypassed to GND with a ceramic capacitor as close to the pin as possible. An electrolytic capacitor may also be used in addition to the ceramic capacitor. A minimum of 0.1-μF ceramic capacitor is required. Additional REF bypassing is required for external loads greater than 2.5 mA on the reference. To prevent noise problems with high-speed switching transients,bypassREFtogroundwithaceramiccapacitorclosetotheICpackage. The UCC2802 and UCC2804 have a 5-V reference. The UCC2803 and UCC2805 have a 4-V reference; both ±1.5% versus ±2% on the UC3842 family. The output short-circuit current is lower 5 mA versus 30 mA. REF must be bypassed to ground with a ceramic capacitor to prevent oscillation and noise problems. REF can be usedasalogicoutput;aswhenVCCislowerthantheUVLOthreshold,REFisheldlow. 9.3.2 UndervoltageLockout(UVLO) The UCC280x devices feature undervoltage lockout protection circuits for controlled operation during power-up and power-down sequences. Both the supply voltage (VCC) and the reference voltage (Vref) are monitored by the UVLO circuitry. An active low, self-biasing totem pole output during UVLO design is also incorporated for enhancedpowerswitchprotection. Undervoltage lockout thresholds for the UCC2802, UCC2803, UCC2804, and UCC2805 devices are different from the previous generation of UCx842, UCx843, UCx844, and UCx845 PWMs. Basically, the thresholds are optimizedfortwogroupsofapplications:off-linepowersuppliesandDC-DCconverters. TheUCC2802andUCC2804featuretypicalUVLOthresholdsof12.5Vforturnonand8.3V for turnoff, providing 4.3Vofhysteresis. For low voltage inputs, which include battery and 5-V applications, the UCC2803 and UCC2805 turn on at 4.1 V andturnoffat3.6Vwith0.5Vofhysteresis. TheUCC2800andUCC2801haveUVLOthresholdsoptimizedforautomotiveandbatteryapplications. During UVLO the IC draws approximately 100 μA of supply current. Once crossing the turnon threshold the IC supplycurrentincreasestypicallytoabout500 μA,overanorderofmagnitudelowerthanbipolarcounterparts. Figure11. ICSupplyCurrentatUVLO 14 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 Table1.UVLOLevelComparisonTable DEVICE Vton(V) Vtoff(V) UCC2800 7.2 6.9 UCC2801 9.4 7.4 UCC2802,UCC2804 12.5 8.3 UCC2803,UCC2805 4.1 3.6 9.3.3 Self-Biasing,ActiveLowOutput The self-biasing, active low clamp circuit shown in Figure 12 eliminates the potential for problematic MOSFET turnon. As the PWM output voltage rises while in UVLO, the P device drives the larger N type switch ON, which clamps the output voltage low. Power to this circuit is supplied by the externally rising gate voltage, so full protectionisavailableregardlessoftheICssupplyvoltageduringundervoltagelockout. 2 V V = OPEN CC V V = 2 V OUT CC V = 0 V CC V = 1 V 1 V CC 50 mA 100 mA I OUT Figure12.InternalCircuitHoldingOUTLow Figure13.OUTVoltagevsOUTCurrent DuringUVLO DuringUVLO 9.3.4 ReferenceVoltage The traditional 5-V amplitude bandgap reference voltage of the UC3842 family can be also found on the UCC2800, UCC2801, UCC2802, and UCC2804 devices. However, the reference voltage of the UCC2803 and UCC2805 device is 4 V. This change was necessary to facilitate operation with input supply voltages below 5 V. Many of the reference voltage specifications are similar to the UC3842 devices although the test conditions have been changed, indicative of lower-current PWM applications. Similar to their bipolar counterparts, the BiCMOS devicesinternallypullthereferencevoltagelowduringUVLO,whichcanbeusedasaUVLOstatusindication. UCC380X REF R 0.1 µF TO BYPASS E/A+ R Copyright © 2016, Texas Instruments Incorporated Figure14. RequiredReferenceBypass Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 15 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com Note that the 4-V reference voltage on the UCC2803 and UCC2805 is derived from the supply voltage (VCC) and requires about 0.5 V of headroom to maintain regulation. Whenever Vcc is below approximately 4.5 V, the reference voltage also drops outside of its specified range for normal operation. The relationship between VCC andV duringthisexcursionisshowninFigure15. REF 4.0 V 3.9 V 3.8 V F E R V 3.7 V 3.6 V 3.5 V 3.6 V 3.8 V 4.0 V 4.2 V 4.4 V 4.6 V 4.8 V 5.0 V V CC Figure15. UCC2803REFOutputvsV VCC The noninverting input to the error amplifier is tied to half of the PWM's reference voltage, V . Note that this REF input is 2 V on the UCC2803 and UCC2805 and 2.5 V on the higher reference voltage parts: the UCC2800, UCC2801,UCC2802,andUCC2804. 9.3.5 Oscillator The UCC280x oscillator generates a sawtooth waveform on RC. The rise time is set by the time constant of R T and C . The fall time is set by C and an internal transistor on-resistance of approximately 130 Ω. During the fall T T time, the output is OFF and the maximum duty cycle is reduced below 50% or 100%, depending on the part number. Larger timing capacitors increase the discharge time and reduce the maximum duty cycle and frequency. REF 8 0.2V + RT R Q + S RC 4 2.65V C T Figure16. OscillatorEquivalentCircuit The oscillator section of the UCC2800 through UCC2805 BiCMOS devices has few similarities to the UC3842 type — other than single pin programming. It does still use a resistor to the reference voltage and capacitor to ground to program the oscillator frequency up to 1 MHz. Timing component values must be changed because a much lower charging current is desirable for low-power operation. Several characteristics of the oscillator have been optimized for high-speed, noise-immune operation. The oscillator peak-to-peak amplitude has been increased to 2.45 V typical versus 1.7 V on the UC3842 family. The lower oscillator threshold has been dropped to approximately 0.2 V while the upper threshold remains fairly close to the original 2.8 V at approximately 2.65V. Discharge current of the timing capacitor has been increased to nearly 20-mA peak as opposed to roughly 8 mA. This can be represented by approximately 130 Ω in series with the discharge switch to ground. A higher current was necessary to achieve brief dead times and high duty cycles with high-frequency operation. Practical applicationscanusethesenewICstoa1-MHzswitchingfrequency. 16 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 2.65 V V CT 0.2 V 0 V f CONV Figure17.OscillatorWaveform 1000 800 600 400 z) 200 H C = 100 p k T ( ƒ 100 80 C = 180 p T 60 C = 270 p T C = 390 p 40 T C = 470 p T 20 0 20 40 60 80 100 120 R (kW) T Figure18. OscillatorFrequencyvsR ForSeveralC T T 9.3.6 Synchronization Synchronization of these PWM controllers is best obtained by the universal technique shown in Figure 19. The ICs oscillator is programmed to free run at a frequency about 20% lower than that of the synchronizing frequency. A brief positive pulse is applied across the 50-Ω resistor to force synchronization. Typically, a 1-V amplitudepulseof100-nswidthissufficientformostapplications. The ICs can also be synchronized to a pulse train input directly to the oscillator RC pin. Note that the IC internally pulls low at this node once the upper oscillator threshold is crossed. This 130-Ω impedance to ground remains active until the pin is lowered to approximately 0.2 V. External synchronization circuits must accommodatetheseconditions. REF R T RC C T SYNC §(cid:3)50 (cid:13)(cid:3) Figure19. SynchronizingtheOscillator Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 17 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com 9.3.7 PWMGenerator Maximum duty cycle is higher for these devices than for their UC384x predecessor. This is primarily due to the higher ratio of timing capacitor discharge to charge current, which can exceed one hundred to one in a typical BiCMOS application. Attempts to program the oscillator maximum duty cycle much below the specified range by adjusting the timing component values of R and C must be avoided. There are two reasons to stay away from T T this design practice. First, the ICs high discharge current would necessitate higher charging currents than necessary for programming, defeating the purpose of low power operation. Secondly, a low-value timing resistor preventsthecapacitorfromdischargingtothelowerthresholdandinitiatingthenextswitchingcycle. 9.3.8 MinimumOff-TimeSetting(Dead-TimeControl) Dead time is the term used to describe the ensured OFF time of the PWM output during each oscillator cycle. It is used to ensure that even at maximum duty cycle, there is enough time to reset the magnetic circuit elements, and prevent saturation. The dead time of the UCC280x PWM family is determined by the internal 130-Ω discharge impedance and the timing capacitor value. Larger capacitance values extend the dead time whereas smaller values results in higher maximum duty cycles for the same operating frequency. A curve for dead time versus timing capacitor values is provided in Figure 20. Increasing the dead time is possible by adding a resistor between the RC pin of the IC and the timing components, as shown in Figure 21. The dead time increases with the discharge resistor value to about 470 Ω as indicated from the curve in Figure 22. Higher resistances must be avoided as they can decrease the dead time and reduce the oscillator peak-to-peak amplitude. Sinking too much current (1 mA) by reducing R will freeze the oscillator OFF by preventing discharge to the lower comparator T threshold voltage of 0.2 V. Adding this discharge control resistor has several impacts on the oscillator programming. First, it introduces a DC offset to the capacitor during the discharge – but not the charging portion of the timing cycle, thus lowering the usable peak-to-peak timing capacitor amplitude. Because of the reduced peak-to-peak amplitude, the exact value of C may require adjustment from UC3842 type designs to obtain the T correct initial oscillator frequency. One alternative is keep the same value timing capacitor and adjust both the timinganddischargeresistorvaluesbecausethesearereadilyavailableinfinernumericalincrements. 200 180 REF 160 RT 140 s) RD (n 120 RC Td <470 (cid:159) 100 CT 80 60 Copyright © 2016, Texas Instruments Incorporated 40 0 125 250 375 500 C (pF) T Figure20.MinimumDeadTimevsC Figure21.CircuittoProduceControlled T MaximumDutyCycle 18 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 100 99 98 97 %) 96 e ( ycl 95 C y Dut 94 x a M 93 92 91 90 89 0 250 500 750 1000 RD, Ohms Figure22. MaximumDutyCyclevsR forR =20kΩ D T 9.3.9 LeadingEdgeBlanking A 100-ns leading edge blanking interval is applied to the current sense input circuitry of the UCC280x devices. This internal feature has been incorporated to eliminate the requirement for an external resistor-capacitor filter network to suppress the switching spike associated with turnon of the power MOSFET. This 100-ns period must be adequate for most switch-mode designs but can be lengthened by adding an external R/C filter. Note that the 100-ns leading edge blanking is also applied to the cycle-by-cycle current limiting function in addition to the overcurrentfaultcomparator. Figure23.CurrentSenseFilterRequired Figure24.CurrentSenseWaveforms WithOlderPWMICs WithLeadingEdgeBlanking 9.3.10 MinimumPulseWidth The leading edge blanking circuitry can lead to a minimum pulse width equal to the blanking interval under certain conditions. This occurs when the error amplifier output voltage (minus a diode drop and divided by 1.65) is lower than the current sense input. However, the amplifier output voltage must also be higher than a diode forward voltage drop of about 0.5 V. It is only during these conditions that a minimum output pulse width equal to the blanking duration can be obtained. Note that the PWM comparator has two inputs; one is from the current sense input. The other PWM input is the error amplifier output that has a diode and two resistors in series to ground. The diode in this network is used to ensure that zero duty cycle can be reached. Whenever the E/A output falls below a diode forward voltage drop, no current flows in the resistor divider and the PWM input goes tozero,alongwithpulsewidth. Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 19 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com + – Figure25. ZeroDutyCycleOffset 9.3.11 CurrentLimiting A 1-V (typical) cycle-by-cycle current limit threshold is incorporated into the UCC280x family. Note that the 100- ns leading edge blanking pulse is applied to this current limiting circuitry. The blanking overrides the current limit comparator output to prevent the leading edge switch noise from triggering a current limit function. Propagation delay from the current limit comparator to the output is typically 70 ns. This high-speed path minimizes power semiconductordissipationduringanoverloadbyabbreviatingtheONtime. For increased efficiency in the current sense circuitry, the circuit shown in Figure 26 can be used. Resistors R A and R bias the actual current sense resistor voltage up, allowing a small current sense amplitude to be used. B Thiscircuitryprovidescurrentlimitingprotectionwithlowerpowerlosscurrentsensing. REF PWM + 0.1 µF 0 RA – V CS TO RCS 0 LOAD Q1 + RB CS – + 0 RCS – Copyright © 2016, Texas Instruments Incorporated Figure26.BiasingCSForLower Figure27.CSPinVoltagewithBiasing CurrentSenseVoltage The example shown uses a 200-mV full scale signal at the current sense resistor. Resistor R biases this up by B approximately700mVtomatewiththe0.9-Vminimumspecificationofthecurrentlimitcomparator of the IC. The value of resistor R changes with the specific IC used, due to the different reference voltages. The resistor A values must be selected for minimal power loss. For example, a 50-µA bias sets R = 13 kΩ, R = 75 kΩ B A (UCCx800,UCC2801,UCC2802,andUCC2804),orR =56kΩwiththeUCC2803andUCC2805devices. A 9.3.12 OvercurrentProtectionandFullCycleRestart A separate overcurrent comparator within the UCC280x devices handle operation into a short-circuited or severely overloaded power supply output. This overcurrent comparator has a 1.5-V threshold and is also gated by the leading edge blanking signal to prevent false triggering. Once triggered, the overcurrent comparator uses the internal soft-start capacitor to generate a delay before retry is attempted. Often referred to as hiccup, this delay time is used to significantly reduce the input and dissipated power of the main converter and switching components. Full Cycle Soft Start ensures that there is a predictable delay of greater than 3 ms between successive attempts to operate during fault. The circuit shown in Figure 28 and the timing diagram in Figure 29 show how the IC responds to a severe fault, such as a saturated inductor. When the fault is first detected, the internal soft-start capacitor instantly discharges and stays discharged until the fault clears. At the same time, the PWM output is turned off and held off. When the fault clears, the capacitor slowly charges and allows the error 20 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 amp output (COMP) to rise. When COMP gets high enough to enable the output, another fault occurs, latching off the PWM output, but the soft-start capacitor still continues to rise to 4 V before being discharged and permitting start of a new cycle. This means that for a severe fault, successive retries is spaced by the time required to fully charge the soft-start capacitor. TI recommends low leakage transformer designs in high- frequency applications to activate the overcurrent protection feature. Otherwise, the switch current may not ramp up sufficiently to trigger the overcurrent comparator within the leading edge blanking duration. This condition would cause continual cyclical triggering of the cycle-by-cycle current limit comparator but not the overcurrent comparator. This would result in brief high power dissipation durations in the main converter at the switching frequency. The intent of the overcurrent comparator is to reduce the effective retry rate under these conditions to afewmilliseconds,thussignificantlyloweringtheshort-circuitpowerdissipationoftheconverter. CS FB COMP 3 2 1 Over-Current Leading Edge Blanking VCC 1.5 V REF/2 OK S Q R 4 V Ref S Q OK R 0.5 V Full Cycle Soft Start t= 5 ms Figure28. DetailedBlockDiagramforOvercurrentProtection Figure29. ICBehavioratRepetitiveFault 9.3.13 SoftStart Internal soft starting of the PWM output is accomplished by gradually increasing error amplifier (E/A) output voltage. When used in current mode control, this implementation slowly raises the peak switch current each PWM cycle in comparison, forcing a controlled start-up. In voltage mode (duty cycle) control, this feature continuallywidensthepulsewidth. Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 21 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com 2 1 3 Leading Edge Blanking REF/2 To Output Logic t= 4ms C SS Figure30. DetailedBlockDiagramforSoft-Start The internal soft-start capacitor (Css) is discharged following an undervoltage lockout transition or if the reference voltage is below a minimum value for normal operation. Additionally, discharge of Css occurs whenever the overcurrent protection comparator is triggered by a fault. Soft start is performed within the UCCx800, UCC2801, UCC2802, UCC2803, UCC2804, and UCC2805 devices by clamping the E/A amplifier outputtoaninternalsoft-startcapacitor(Css),whichischargedbya current source. The soft-start clamp circuitry isoverriddenonceCsschargesabovethevoltagecommandedbytheerroramplifierfornormalPWMoperation. RC 0 Soft Start 0 PWM 0 CS 0 Figure31. ICSoft-StartBehavior 22 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 9.3.14 SlopeCompensation Slope compensation can be added in all current mode control applications to cancel the peak to average current error. Slope compensation is necessary with applications with duty cycles exceeding 50%, but also improves performance in those below 50%. Primary current is sensed using resistor Rcs in series with the converter switch. The timing resistor can be broken up into two series resistors to bias up the NPN follower. This is required to provide ample compliance for slope compensation at the beginning of a switching cycle, especially with continuous current converters. A NPN voltage follower drives the slope compensating programming resistor (Rsc)toprovideaslopecompensatingcurrentintoC . F REF R T To Main RC Switch C T R SC R F CS C R F CS Figure32. AddingSlopeCompensation 9.4 Device Functional Modes TheUCC280xfamilyofhigh-speed,low-powerintegratedcircuitshasthefollowingfunctionmodes. 9.4.1 NormalOperation During this operation mode, IC controls the power converter into the voltage mode or current mode control, regulate the output voltage or current through the converter duty cycle. The regulation can be achieve through theintegratederroramplifierorexternalfeedbackcircuitry. 9.4.2 UVLOMode During the system start-up, VCC voltage starts to rise from 0. Before the VCC voltage reaches its corresponding turn on threshold, the IC is operate under UVLO mode. In this mode, REF pin voltage is not generated. When VCC is above 1 V and below the turn on threshold, the RFE pin is actively pulled low through a 5-kΩ resistor. Thisway,REFpincanbeusedasalogicsignaltoindicateUVLOmode. 9.4.3 SoftStartMode Once VCC voltage rises across the UVLO level, or comes out of a fault mode, it enters the soft start mode. During soft start, the internal soft start capacitor C clamps the error amplifier output voltage, forces it rise SS slowly. This in turn controls the power converter peak current rising slowly, reducing the voltage and current stresstothesystem.TheUCC280xfamilyhasafixedbuildinsoft-starttimeat4ms. 9.4.4 FaultMode A separate overcurrent comparator within the UCC280x devices handles operation into a short-circuited or severely overloaded power supply output. This overcurrent comparator has a 1.5-V threshold and is also gated by the leading edge blanking signal to prevent false triggering. When the fault is first detected, the internal soft- start capacitor instantly discharges and stays discharged until the fault clears. At the same time, the PWM output is turned off and held off. This is often referred to as hiccup. This delay time is used to significantly reduce the input and dissipated power of the main converter and switching components. Full cycle soft start insures that there is a predictable delay of greater than 3 milliseconds between successive attempts to operate during fault. Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 23 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com Device Functional Modes (continued) When the fault clears, the capacitor slowly charges and allows the error amp output (COMP) to rise. When COMP gets high enough to enable the output, another fault occurs, latching off the PWM output, but the soft- start capacitor still continues to rise to 4 V before being discharged and permitting start of a new cycle. This means that for a severe fault, successive retries are spaced by the time required to fully charge the soft-start capacitor. 24 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 10 Application and Implementation NOTE Information in the following applications sections is not part of the TI component specification, and TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining suitability of components for their purposes. Customers should validateandtesttheirdesignimplementationtoconfirmsystemfunctionality. 10.1 Application Information The UCC280x controllers are peak current mode (PCM) pulse width modulators (PWM). These controllers have an onboard amplifier and can be used in isolated and non-isolated power supply design. There is an onboard totem-pole gate driver capable of delivering 1 A of peak current. This is a high-speed PWM capable of operating atswitchingfrequenciesupto1MHz. 10.2 Typical Application Figure 33 illustrates a typical circuit diagram for an AC-DC converter using the UCC2800 in a peak current mode controlledflybackapplication. DCL FA VIN = 85 to 265V AC 5A – ~ + DA CCL 10 nF RCL 50 k(cid:159) DC VOUT+ ~ CIN CVCC2 NP COUT 120 uF RH 300 k(cid:159) DB RD QA VOUT- 22 VO NA RG 10 RCS RZ 1 k(cid:159) RAC U1 RLED VO¶ UCC2800 1 COMP REF 8 RT CFB RFB2 10 N(cid:159)(cid:3) 2 FB VCC 7 DC 10VRJ 1 k(cid:159) 3 CS OUT 6 CVCC1 CVREF 1µF 1µF VC 4 RC GND 5 RCSF U2 RRAMP CT CCSF RP RFBU 270 pF RFB1 RZ CZ CRAMP 10 nF 4.99 k(cid:159) U3 REG 1 k(cid:159) TL431 RFBB Copyright © 2016, Texas Instruments Incorporated Figure33. TypicalApplicationCircuit Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 25 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com Typical Application (continued) 10.2.1 DesignRequirements Use the parameters in Table 2 to review the design of a 12-V, 48-W offline flyback converter using UCC2800 PWMcontroller. Table2.DesignSpecifications PARAMETER CONDITIONS MIN NOM MAX UNIT INPUTCHARACTERISTICS V Inputvoltage(RMS) 85 265 V IN f Linefrequency 47 63 Hz LINE OUTPUTCHARACTERISTICS V Outputvoltage 11.75 12 12.25 V OUT V Outputripplevoltage 120 mV ripple PP I Outputcurrent 4 4.33 A OUT V Outputtransient Outputvoltagemeasuredunder0-Ato4-Aloadstep 11.75 12.25 V tran SYSTEMCHARACTERISTICS η Maxloadefficiency 85% 10.2.2 DetailedDesignProcedure Thedesignstartswithselectinganappropriatebulkcapacitor. The primary side bulk capacitor is selected based on the power level. Based on the desired minimum bulk voltagelevel,thebulkcapacitorvaluecanbecalculatedasEquation8. “ 1 § VBULK(min) •” 2PINu«0.25(cid:14) uarcsin¤ ‚» CBULK (cid:11)2V«‹2IN(min)S(cid:16)V2BULK¤'(m2in)u(cid:12)uVfINLI(NmEin)‚„»… (8) In Equation 8, P is the maximum output power divided by target efficiency, V is the minimum AC input IN IN(min) voltageRMSvalue.V isthetargetminimumbulkvoltage,andf isthelinefrequency. BULK(min) LINE Based on the equation, to achieve 75-V minimum bulk voltage, assuming 85% converter efficiency and 47-Hz minimum line frequency, the bulk capacitor must be larger than 127 µF and 180 µF was chosen in the design, consideringthetoleranceofthecapacitors. The transformer design starts with selecting a suitable switching frequency. Generally the switching frequency selection is based on the tradeoff between the converter size and efficiency, based on the simple Flyback topology. Normally, higher switching frequency results in smaller transformer size. However, the switching loss is going to be increased and hurts the efficiency. Sometimes, the switching frequency is selected to avoid certain communication band to prevent the noise interference with the communication. The frequency selection is beyondthescopeofthisdatasheet. The switching frequency is selected as 110 kHz, to minimize the transformer size. At the same time, the regulationsstarttohave limit on EMI noise at 150 kHz, design 110-kHz switching frequency can help to minimize theEMIfiltersize. Thenthe transformer turns ratio can be selected based on the desired MOSFET voltage rating and diode voltage rating.Becausemaximuminputvoltageis265VAC,thepeakvoltagecanbecalculatedasEquation9. V = 2´V »375V BULK(max) IN(max) (9) To minimize the cost of the system, the popular 650-V MOSFET is selected. Considering the design margin and extra voltage ringing on the MOSFET drain, the reflected output voltage must be less than 120 V. The transformerturnsratiocanbeselectedasEquation10. 120V n = =10 ps 12V (10) 26 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 The diode voltage stress is the output voltage plus the reflected input voltage. The voltage stress on the diode canbecalculatedasEquation11. V 375V V = BULK(max)+V = (cid:14)(cid:20)(cid:21)9§(cid:24)(cid:19)9 DIODE n OUT 10 ps (11) Considertheringingvoltagespikesandvoltagederatingthediodevoltageratingmustbehigherthan50V. The transformer inductance selection is based on the CCM condition. Larger inductor would allow the converter stays in CCM longer. However, it tends to increase the transformer size. Normally, the transformer magnetizing inductor is selected so that the converter enters CCM operation at about 50% load at minimum line voltage. This would be a tradeoff between the transformer size and the efficiency. In this particular design, due to the higher output current, it is desired to keep the converter deeper in the CCM and minimize the conduction loss and outputripple.TheconverterentersCCMoperationatabout10%loadatminimumbulkvoltage. TheinductorcanbecalculatedasEquation12. 2 æ ö n V V2 ´ç PS OUT ÷ L = 1 BULK(min) çèVBULK(min) +nPSVOUT ÷ø m 2 10%´PIN´ fSW (12) In this equation, the switching frequency is 110 kHz. Therefore, the transformer inductance must be about 1.7mH.1.5mHischosenasthemagnetizinginductorvalue. The auxiliary winding provides the power for UCC2800 normal operation. The auxiliary winding voltage is the output voltage reflected to the primary side. It is desired to have higher reflected voltage so that the IC can quickly get energy from the transformer and make the heavy load startup easier. However, the high the reflect voltagemakestheICconsumesmorepower.Therefore,tradeoffisrequired. In this design, the auxiliary winding voltage is selected the same as the output voltage so that it is above the UVLO level and keep the IC and driving loss low. Therefore, the auxiliary winding to the output winding turns ratioisselectedasEquation13. 12V n = =1 as 12V (13) Based on calculated inductor value and the switching frequency, the current stress of the MOSFET and diode canbecalculated. ThepeakcurrentoftheMOSFETcanbecalculatedasEquation14. n V PS OUT P 1V V +n V IN BULK(min) BULK:min; PS OUT I = + × PKMOS n V 2 L f V × PS OUT m sw BULK:min; V +n V BULK:min; PS OUT (14) TheMOSFETpeakcurrentis1.425A. ThediodepeakcurrentisthereflectedMOSFETpeakcurrentonthesecondaryside. I =n ´I =14.25A PKDIODE ps PKMOS (15) TheRMScurrentoftheMOSFETcanbecalculatedasEquation16. I = 1D3 ´æçVBULK(min)ö÷2 -D2IPKMOSVBULK(min) +D´I2 RMSMOS 3 çè Lm´ fsw ÷ø Lm´ fsw PKMOS (16) InEquation16,DistheMOSFETdutycycleatminimumbulkvoltageanditcanbecalculatedasEquation17. n V D= ps OUT V +n V BULK(min) ps OUT (17) TheMOSFETRMScurrentis0.75A.Therefore,IRFB9N65AisselectedasprimarysideMOSFET. Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 27 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com The diode average current is the output current 4 A with 60-V rating and 14.25-A peak current capability, 48CTQ060-1isselected. Output capacitor is selected based on the output voltage ripple requirement. In this design, 0.1% voltage ripple is assumed.Basedonthe0.1%ripplerequirement,thecapacitorvaluecanbeselectedbasedonEquation18. n V ps OUT I ´ OUT V +n V BULK(min) ps OUT C ³ =2105mF OUT 0.1%´VOUT ´ fsw (18) Consider the tolerance and temperature effect, together the ripple current rating of the capacitors, the output capacitorof3of680µFinparallelwasselected. Afterthepowerstageisdesigned,thesurroundcomponentscanbeselected. 10.2.2.1 CurrentSensingNetwork The current sensing network consists of R , R , C , and optional R . Typically, the direct current sense CS CSF CSF P signal contains a large amplitude leading edge spike associated with the turnon of the main power MOSFET, reverse recovery of the output rectifier, and other factors including charging and discharging of parasitic capacitances. Therefore, C and R form a low-pass filter that provides additional immunity beyond the CSF CSF internal blanking time to suppress the leading edge spike. For this converter, C is chosen to be 270 pF to CSF provideenoughfiltering. Without R , R sets the maximum peak current in the transformer primary based on the maximum amplitude of P CS CSpin,1V.Toachieve1.425-Aprimarysidepeakcurrent,a0.75-Ω resistorischosenforR . CS The high current sense threshold help to provide better noise immunity but the current sense loss is increased. The current sense loss can be minimized by injecting offset voltage into the current sense signal. R and R P CS form a resistor divider network from the current sense signal to the device’s reference voltage to offset the current sense voltage. This technique still achieves current mode control with cycle-by-cycle overcurrent protection.Tocalculaterequiredoffsetvalue(Voffset),useEquation19. RCSF Voffset VREF RCSF(cid:14)RP (19) 10.2.2.2 GateDriveResistor R is the gate driver resistor for the power switch, Q . The selection of this resistor value must be done in G A conjunction with EMI compliance testing and efficiency testing. Larger R slows down the turnon and turnoff of G the MOSFET. Slower switching speed reduces EMI but also increases the switching loss. A tradeoff between switching loss and EMI performance must be carefully performed. For this design, 10 Ω was chosen as the gate driverresistor. 10.2.2.3 VrefCapacitor A precision 5-V reference voltage is designed to perform several important functions. The reference voltage is divided down internally to 2.5 V and connected to the error amplifier’s noninverting input for accurate output voltage regulation. Other duties of the reference voltage are to set internal bias currents and thresholds for functions such as the oscillator upper and lower thresholds along with the overcurrent limiting threshold. Therefore, the reference voltage must be bypassed with a ceramic capacitor (C ), and 1-μF, 16-V ceramic VREF capacitor was selected for this converter. Placement of this capacitor on the physical printed-circuit board layout mustbeascloseaspossibletotherespectiveREFandGNDpinsaspossible 10.2.2.4 R C T T The internal oscillator uses a timing capacitor (C ) and a timing resistor (R ) to program operating frequency and T T maximum duty cycle. The operating frequency can be programmed based the curves in Figure 3, where the timing resistor can be found once the timing capacitor is selected. The selection of timing capacitor also affects the maximum duty cycle provided in Figure 5. It is best for the timing capacitor to have a flat temperature coefficient, typical of most COG or NPO type capacitors. For this converter, 13.6 kΩ and 1000 pF were selected forR andC tooperateat110-kHzswitching. T T 28 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 10.2.2.5 Start-UpCircuit At startup, the IC gets its power directly from the high voltage bulk, through a high voltage resistor R . The H selection of start-up resistor is the tradeoff between power loss and start-up time. The current flowing through R H at minimum input voltage must be higher than the VCC current under UVLO condition (0.2 mA at its maximum value).A150-kΩ resistorischosenastheresultofthetradeoff. After VCC is charged up above UVLO on threshold, UCC2800 starts to operate and consumes full operating current. At the beginning, because the output voltage is low, VCC cannot get energy from the auxiliary winding. VCC capacitor requires to hold enough energy to prevent its voltage drop below UVLO during start-up time, before output reaches high enough. A larger capacitor holds more energy but slows down the start-up time. In thisdesign,a120-µFcapacitorischosentoprovideenoughenergyforthestart-uppurpose. 10.2.2.6 VoltageFeedbackCompensation Feedback compensation, also called closed-loop control, reduces or eliminates steady state error, reduces the sensitivity to parametric changes, changes the gain or phase of a system over some desired frequency range, reduces the effects of small signal load disturbances and noise on system performance, and creates a stable system. The following section describes how to compensate an isolated Flyback converter with the peak current modecontrol. 10.2.2.6.1 PowerStageGain,Zeroes,andPoles The first step in compensating a fixed frequency flyback is to verify if the converter is continuous conduction mode (CCM) or discontinuous conduction mode (DCM). If the primary inductance, L , is greater than the P inductance for DCM, CCM boundary mode operation, called the critical inductance, or L , then the converter Pcrit operatesinCCMcalculatedwithEquation20. R ´N2 æ V ö2 LPcrit = O2U´Tf PS ´çV +V IN ´N ÷ SW è IN OUT PS ø (20) For the entire input voltage range, the selected inductor has value larger than the critical inductor. Therefore, the converteroperatesinCCMandthecompensationlooprequiresdesignbasedonCCMflybackequations. The current-to-voltage conversion is done externally with the ground-referenced current sense resistor, R , and CS the internal resistor divider sets up the internal current sense gain, A = 1.65. The IC technology allows the CS tightcontroloftheresistordividerratio,regardlessoftheactualresistorvaluevariations. The DC open-loop gain, G , of the fixed-frequency voltage control loop of a peak current mode control CCM O flyback converter shown in Figure 33 is approximated by first using the output load, R , the primary to OUT secondaryturnsratio,N ,themaximumdutycycle,D,calculatedinEquation21. PS R ´N 1 G = OUT PS ´ O RCS´ACS (1-D)2 +(2´M)+1 t L (21) In Equation 21, D is calculated with Equation 22, τ is calculated with Equation 23, and M is calculated with L Equation24. N ´V D= PS OUT V +(N ´V ) IN PS OUT (22) 2´L ´f t = P SW L R ´N2 OUT PS (23) V ´N M= OUT PS V IN (24) For this design, a converter with an output voltage V of 12 V, and 48 W relates to an output load, R , equal OUT OUT to3 Ωatfullload. At minimum input voltage of 75 V DC, the duty cycle reaches it maximum value of 0.615. The current sense resistance, R , is 0.75 Ω, and a primary to secondary turns-ratio, N is 10. The open-loop gain calculates to CS PS 14.95dB. Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 29 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com A CCM flyback has two zeroes that are of interest. The ESR and the output capacitance contribute a left-half planezerotothepowerstage,andthefrequencyofthiszero,f ,arecalculatedwithEquation25. ESRz 1 w = ESRz R ´C ESR OUT (25) The f zero for a capacitance bank of three 680-µF capacitors for a total output capacitance of 2040 µF and a ESRz totalESRof13mΩisplacedat6kHz. CCM flyback converters have a zero in the right-half plane, RHP, in their transfer function. RHP zero has the same 20 dB/decade rising gain magnitude with increasing frequency just like a left-half plane zero, but it adds phase lag instead of lead. This phase lag tends to limit the overall loop bandwidth. The frequency location, f RHPz in Equation 26, is a function of the output load, the duty cycle, the primary inductance, L , and the primary to P secondarysideturnsratio,N . PS R ´(1-D)2 ´N2 f = OUT PS RHPz 2´p´L ´D P (26) Right half plane zero frequency increases with higher input voltage and lighter load. Generally, the design requires consideration of the worst case of the lowest right half plane zero frequency and the converter must be compensated at the minimum input and maximum load condition. With a primary inductance of 1.5 mH, at 75-V DCinput,theRHPzerofrequency,f ,isequalto7.65kHzatmaximumdutycycle,fullload. RHPz The power stage has one dominate pole, ω , which is in the region of interest, placed at a lower frequency, f , P1 P1 which is related to the duty cycle, D, the output load, and the output capacitance. There is also a double pole placedathalftheswitchingfrequencyoftheconverter,f calculatedwithEquation27andEquation28. P2 (1-D)3 +1+D t f = L P1 2´p´R ´C OUT OUT (27) f f = SW P2 2 (28) Slope compensation is the large signal sub-harmonic instability that can occur with duty cycles that extends beyond 50%. The subharmonic oscillation increases the output voltage ripple and sometimes it even limits the powerhandlingcapabilityoftheconverter. The target of slope compensation is to achieve idea quality coefficient, Q , at half of the switching frequency to p be1.TheQ iscalculatedwithEquation29. p 1 Q = P p´éëMC´(1-D)-0.5ùû (29) In Equation 29, D is the primary side switch duty cycle and M is the slope compensation factor, which is defined C withEquation30. S M =1+ e C S n (30) In Equation 30, Se is the compensation ramp slope and the S is the inductor rise slope. The optimal goal of the n slope compensation is to achieve Q equal to 1, which mean M must be 2.128 when D reaches it maximum P C valueof0.615. TheinductorrisesloponCSpiniscalculatedwithEquation31. V ×R 75V×0.75(cid:13) BULK(min) CS S = = =38mV/(cid:29)s n L 1.5mH P (31) ThecompensationslopeiscalculatedwithEquation32. S =(M -1)´S =(2.128-1)´38mV/ms=46.3mV/ms e C n (32) 30 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 The compensation slope is added into the system through R and R . The C is selected to RAMP CSF RAMP approximate high frequency short circuit. Choose C as 10 nF as the starting point, and make adjustments if RAMP required. The R and R forms a voltage divider from the RC pin ramp voltage and inject the slope RAMP CSF compensation into CS pin. Choose R much larger than the R resistor so that it won’t affect much the RAMP T frequency setting. In this design, R is selected as 24.9 kΩ. The RC pin ramp slope is calculated with RAMP Equation33. S =2.4 V´100kHz=240mV/ms RC (33) Toachieve46.3mV/µscompensationslope,R resistoriscalculatedwithEquation34. CSF R = RRAMP = 24.9kW =5.95kW CSF S 240mV/ms RC -1 -1 R 46.3mV/ms e (34) The power stage open-loop gain and phase can be plotted as a function of frequency. The total gain, as a functionoffrequencycanbecharacterizedwithEquation35. æ S ö æ S ö ç1+ ÷´ç1- ÷ H (S)=G ´è wESRz ø è wRHPz ø´ 1 0 0 1+ s(f) 1+ S + S2 wP1 wP2´QP wP22 (35) Thebodeisplottedaccordingly(seeFigure34andFigure35). 20 0 -30 10 -60 Loop Gain (dB) -100 Phase (Degree) -90 -120 -20 -150 -180 -30 1 10 100 1k 10k 100k 1 10 100 1k 10k 100k Frequency (Hz) Frequency (Hz) Figure34.ConverterOpenLoopBodePlot-Gain Figure35.ConverterOpenLoopBodePlot-Phase 10.2.2.6.2 CompensationLoop For good transient response, the bandwidth of the finalized design must be as large as possible. The bandwidth ofaCCMflyback,f ,islimitedto¼oftheRHPzerofrequency,orapproximately1.9kHzusingEquation36. BW f f = RHPz BW 4 (36) The gain of the open-loop power stage at f is equal to –22.4 dB and the phase at f is equal to –87°. First BW BW step is to choose the output voltage sensing resistor values. The output sensing resistors are selected based on theallowedpowerconsumptionandinthiscase,1mAofsensingcurrentisassumed. The TL431 is used as the feedback amplifier. Given its 2.5-V reference voltage, the voltage sensing dividers R andR canbeselectedwithEquation37andEquation38. FBU FBB V -2.5 V R = OUT =9.5kW FBU 1mA (37) Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 31 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com 2.5 V R = =2.5kW FBB 1mA (38) Next step is to put the compensator zero f at 190 Hz, which is 1/10 of the crossover frequency. Choose C as CZ Z afixedvalueof10nFandchoosethezeroresistorvalueaccordingtoEquation39. 1 1 R = = =83.77kW Z 2p´f ´C 2p´190Hz´10nF CZ Z (39) Then put a pole at the lower frequency of right half plane zero or the ESR zero. Based previous analysis, the right half plane zero is at 7.65 kHz and the ESR zero is at 6 kHz, the pole of the compensation loop must be put at 6 kHz. This pole can be added through the primary side error amplifier. R and C provide the necessary FB FB pole.ChoosingR as10kΩ andtheC isselectedwithEquation40. FB FB 1 C = =2.65nF FB 2p´10kW´6kHz (40) Based on the compensation loop structure, the entire compensation loop transfer function is written as Equation41. 1 1+S×C ×R R 1 G(S)= × Z Z × FB2 × ×CTR×R R ×R S×C R S×C ×R +1 EG FBT LED Z FB1 FB FB2 (41) In this equation, the CTR is the current transfer ratio of the opto-coupler. Choose 1 as the nominal value for CTR. R is the opto-pulldown resistor and 1 kΩ is chosen as a default value. The only value required in this EG equation is R . The entire loop gain must be equal to 1 at the crossover frequency. R is calculated LED LED accordinglyas1.62kΩ. The final close loop bode plots are show in Figure 36 and Figure 37. The converter achieves approximately 2- kHzcrossoverfrequencyandapproximately70oofphasemargin. TI recommends checking the loop stability across all the corner cases including component tolerances to ensure systemstability. 100 -100 80 60 -120 Loop Gain (dB) 2400 Phase (Degree)-140 0 -160 -20 -40 -180 1 10 100 1k 10k 100k 1 10 100 1k 10k 100k Frequency (Hz) Frequency (Hz) Figure36.ConverterCloseLoopBodePlot–Gain Figure37.ConverterCloseLoopBodePlot–Phase 32 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 10.2.3 ApplicationCurves Figure38.PrimarySideMOSFETDraintoSourceVoltage Figure39.PrimarySideMOSFETDraintoSourceVoltage at240-VACInput(100V/div) at120-VACInput(100V/div) Figure40.OutputVoltageDuring0.9-Ato2.7-ALoad Figure41.OutputVoltageRippleatFullLoad(100mV/div) Transient(CH1:OutputVoltageACCoupled,200mV/div; CH4:OutputCurrent,1A/div) Figure42.OutputVoltageBehavioratFullLoadStart-up(5V/div) Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 33 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com 11 Power Supply Recommendations An internal VCC shunt regulator is incorporated in each member of the UCC280x PWMs to regulate the supply voltage at approximately 13.5 V. A series resistor from VCC to the input supply source is required with inputs above 12 V to limit the shunt regulator current. A maximum of 10 mA can be shunted to ground by the internal regulator. The internal regulator in conjunction with the device’s low start-up and operating current can greatly simplify powering the device and may eliminate the requirement for a regulated bootstrap auxiliary supply and winding in many applications. The supply voltage is MOSFET gate level compatible and requires no external Zener diode or regulator protection with a current-limited input supply. The UVLO start-up threshold is 1 V below the shunt regulator level on the UCC2802 and UCC2804 devices to ensure start-up. It is important to bypass the ICs supply (VCC) and reference voltage (REF) pins with a 0.1-µF to 1-µF ceramic capacitor to ground. The capacitorsmustbeplacedasclosetotheactualpin connections as possible for optimal noise filtering. A second, larger filter capacitor may also be required in offline applications to hold the supply voltage (VCC) above the UVLOturnoffthresholdduringstart-up. The UVLO start threshold of the UCC280-[2,4] devices has a range of 11.5 V to 13.5 V, while the protection zener voltage can vary from 12 V to 15 V. However, the absolute maximum supply voltage of the IC is specified at 12 V. This absolute maximum is defined as the lowest possible Zener voltage when driven from a low impedance (voltage) source. The zener voltage is always higher than the UVLO start voltage. These two parameterstrackeachotherandthechipistestedtoguaranteethattheZenervoltagewillnever be below that of the start voltage. To limit the current flowing in the internal clamp zener, a series resistor must be added. Failure to provide a series resistance between the auxiliary voltage source and the Vcc pin of the controller, to limit the currentand voltage stress within rated levels on the Vcc pin may result in permanent damage to the controller. In automotive or industrial applications where there is a risk of high power load transients which may cause transients or voltage excursions on the Vcc rail supplying the PWM controller it is recommended to add an external Zener diode across the Vcc pin. The external Zener acts as an additional protection to the impedance providedbytheseriesresistorbetweentheVccsourceandVccpin. Placing a resistor, Rg, in series with the gate of the mosfet allows the mosfet switching speed to be adjusted and alsocanbeusedtokeepthepeakgatedrivecurrentswithinthespecifiedlimitsofthecontroller. HV DC BUS Rstart Bootstrap Rvcc To Output VCC REF Caux UCC280x OUT Rg 1uF External 13V Zener (Recommended 0.1uF when there is a risk of Rcs transients on bias supply) Figure43. DifferentWaysofPoweringUptheDevice 12 Layout 12.1 Layout Guidelines In addition to following general power management IC layout guidelines (star grounding, minimal current loops, reasonableimpedancelevels,andsoon)layoutfortheUCC280xfamilymustconsiderthefollowing: • If possible, a ground plane must be used to minimize the voltage drop on the ground circuit and the noise introducedbyparasiticinductancesinindividualtraces. 34 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 Layout Guidelines (continued) • A decoupling capacitor is required for both the VCC pin and REF pin and both must be returned to GND as closetotheICaspossible. • For the best performance, keep the timing capacitor lead to GND as short and direct as possible. If possible, useseparategroundtracesforthetimingcapacitorandallotherfunctions. • The CS pin filter capacitor must be as close to the IC possible and grounded right at the IC ground pin. This ensuresthebestfilteringeffectandminimizesthechanceofcurrentsensepinmalfunction. •GatedriverloopareamustbeminimizedtoreducetheEMInoisebecauseofthehighdi/dtcurrentintheloop. Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 35 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com 12.2 Layout Example MOSFET Heatsink Track To TO-220FP Bottom View <= (cid:17)(cid:181)ol(cid:3)(cid:18)(cid:2)(cid:137)(cid:3)5 RCS1 S G 6 ½ RCS2 P Track To R Transformer => I W FBG in D d RSNUB1 in g RSNUB2 ½ P R Track To CSNUB I Win <= Bulk Cap + d in g 4 22AWG Jumper T Wire R RCSF A N CCSF S F O CT R M > GND RC CRAMP E = R = RG OUT CS RRAMP n UCC2800 o CVCC3 VCC FB 2 CVCC2 i t c REF COMP A e U ir CREF RFB2 Aux Cap X W D in er RT CFB din g ld RCSO RFB1 CVCC1 1 o S REG e v 22AWG Jumper Wires a E K W OPTO-ISOLATOR C A PCB Bottom-side View Copyright © 2016, Texas Instruments Incorporated Figure44. UCC2800LayoutExample 36 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 www.ti.com SLUS270G–MARCH1999–REVISEDMAY2020 13 Device and Documentation Support 13.1 Community Resources TI E2E™ support forums are an engineer's go-to source for fast, verified answers and design help — straight fromtheexperts.Searchexistinganswersoraskyourownquestiontogetthequickdesignhelpyouneed. Linked content is provided "AS IS" by the respective contributors. They do not constitute TI specifications and do notnecessarilyreflectTI'sviews;seeTI'sTermsofUse. 13.2 Trademarks E2EisatrademarkofTexasInstruments. Allothertrademarksarethepropertyoftheirrespectiveowners. 13.3 Related Links The table below lists quick access links. Categories include technical documents, support and community resources,toolsandsoftware,andquickaccesstoordernow. Table3.RelatedLinks TECHNICAL TOOLS& SUPPORT& PARTS PRODUCTFOLDER ORDERNOW DOCUMENTS SOFTWARE COMMUNITY UCC2800 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2801 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2802 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2803 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2804 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2805 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2800 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2801 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2802 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2803 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2804 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2805 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2800 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2801 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2802 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2803 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2804 Clickhere Clickhere Clickhere Clickhere Clickhere UCC2805 Clickhere Clickhere Clickhere Clickhere Clickhere 13.4 Electrostatic Discharge Caution Thesedeviceshavelimitedbuilt-inESDprotection.Theleadsshouldbeshortedtogetherorthedeviceplacedinconductivefoam duringstorageorhandlingtopreventelectrostaticdamagetotheMOSgates. 13.5 Glossary SLYZ022—TIGlossary. Thisglossarylistsandexplainsterms,acronyms,anddefinitions. Copyright©1999–2020,TexasInstrumentsIncorporated SubmitDocumentationFeedback 37 ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 UCC2800,UCC2801,UCC2802,UCC2803,UCC2804,UCC2805 SLUS270G–MARCH1999–REVISEDMAY2020 www.ti.com 14 Mechanical, Packaging, and Orderable Information The following pages include mechanical, packaging, and orderable information. This information is the most current data available for the designated devices. This data is subject to change without notice and revision of thisdocument.Forbrowser-basedversionsofthisdatasheet,refertotheleft-handnavigation. 38 SubmitDocumentationFeedback Copyright©1999–2020,TexasInstrumentsIncorporated ProductFolderLinks:UCC2800UCC2801 UCC2802 UCC2803 UCC2804 UCC2805 UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805UCC2800 UCC2801 UCC2802 UCC2803 UCC2804 UCC2805

PACKAGE OPTION ADDENDUM www.ti.com 12-May-2020 PACKAGING INFORMATION Orderable Device Status Package Type Package Pins Package Eco Plan Lead/Ball Finish MSL Peak Temp Op Temp (°C) Device Marking Samples (1) Drawing Qty (2) (6) (3) (4/5) 5962-9451301MPA ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 9451301MPA UCC1801 5962-9451302MPA ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 9451302MPA UCC1802 5962-9451303MPA ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 9451303MPA UCC1803 5962-9451304MPA ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 9451304MPA UCC1804 5962-9451305MPA ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 9451305MPA UCC1805 UCC1800J ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 UCC1800J UCC1800J883B ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 UCC1800J/ 883B UCC1800L883B ACTIVE LCCC FK 20 1 TBD POST-PLATE N / A for Pkg Type -55 to 125 UCC1800L/ 883B UCC1801J ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 UCC1801J UCC1801J883B ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 9451301MPA UCC1801 UCC1802J ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 UCC1802J UCC1802J883B ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 9451302MPA UCC1802 UCC1803J ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 UCC1803J UCC1803J883B ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 9451303MPA UCC1803 UCC1804J ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 UCC1804J UCC1804J883B ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 9451304MPA UCC1804 UCC1805J ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 UCC1805J UCC1805J883B ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -55 to 125 9451305MPA UCC1805 Addendum-Page 1

PACKAGE OPTION ADDENDUM www.ti.com 12-May-2020 Orderable Device Status Package Type Package Pins Package Eco Plan Lead/Ball Finish MSL Peak Temp Op Temp (°C) Device Marking Samples (1) Drawing Qty (2) (6) (3) (4/5) UCC2800D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2800 & no Sb/Br) UCC2800DG4 ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2800 & no Sb/Br) UCC2800DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2800 & no Sb/Br) UCC2800DTRG4 ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2800 & no Sb/Br) UCC2800N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type -40 to 85 UCC2800N & no Sb/Br) UCC2800PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR -40 to 85 2800 & no Sb/Br) UCC2801D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2801 & no Sb/Br) UCC2801DG4 ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2801 & no Sb/Br) UCC2801DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2801 & no Sb/Br) UCC2801DTRG4 ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2801 & no Sb/Br) UCC2801N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type -40 to 85 UCC2801N & no Sb/Br) UCC2801PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR -40 to 85 2801 & no Sb/Br) UCC2802D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2802 & no Sb/Br) UCC2802DG4 ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2802 & no Sb/Br) UCC2802DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2802 & no Sb/Br) UCC2802J ACTIVE CDIP JG 8 1 TBD Call TI N / A for Pkg Type -40 to 85 UCC2802J UCC2802N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type -40 to 85 UCC2802N & no Sb/Br) UCC2802NG4 ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type -40 to 85 UCC2802N & no Sb/Br) Addendum-Page 2

PACKAGE OPTION ADDENDUM www.ti.com 12-May-2020 Orderable Device Status Package Type Package Pins Package Eco Plan Lead/Ball Finish MSL Peak Temp Op Temp (°C) Device Marking Samples (1) Drawing Qty (2) (6) (3) (4/5) UCC2802PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR -40 to 85 2802 & no Sb/Br) UCC2803D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2803 & no Sb/Br) UCC2803DG4 ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2803 & no Sb/Br) UCC2803DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2803 & no Sb/Br) UCC2803DTRG4 ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2803 & no Sb/Br) UCC2803N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type -40 to 85 UCC2803N & no Sb/Br) UCC2803PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR -40 to 85 2803 & no Sb/Br) UCC2803PWTR ACTIVE TSSOP PW 8 2000 Green (RoHS NIPDAU Level-2-260C-1 YEAR -40 to 85 2803 & no Sb/Br) UCC2804D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2804 & no Sb/Br) UCC2804DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2804 & no Sb/Br) UCC2804DTRG4 ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2804 & no Sb/Br) UCC2804N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type -40 to 85 UCC2804N & no Sb/Br) UCC2804PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR -40 to 85 2804 & no Sb/Br) UCC2804PWTR ACTIVE TSSOP PW 8 2000 Green (RoHS NIPDAU Level-2-260C-1 YEAR -40 to 85 2804 & no Sb/Br) UCC2805D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2805 & no Sb/Br) UCC2805DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2805 & no Sb/Br) UCC2805DTRG4 ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM -40 to 85 UCC2805 & no Sb/Br) UCC2805N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type -40 to 85 UCC2805N & no Sb/Br) Addendum-Page 3

PACKAGE OPTION ADDENDUM www.ti.com 12-May-2020 Orderable Device Status Package Type Package Pins Package Eco Plan Lead/Ball Finish MSL Peak Temp Op Temp (°C) Device Marking Samples (1) Drawing Qty (2) (6) (3) (4/5) UCC2805PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR -40 to 85 2805 & no Sb/Br) UCC2805PWG4 ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR -40 to 85 2805 & no Sb/Br) UCC2805PWR ACTIVE TSSOP PW 8 2000 Green (RoHS NIPDAU Level-2-260C-1 YEAR -40 to 85 2805 & no Sb/Br) UCC3800D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3800 & no Sb/Br) UCC3800DG4 ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3800 & no Sb/Br) UCC3800DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3800 & no Sb/Br) UCC3800N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type 0 to 70 UCC3800N & no Sb/Br) UCC3800NG4 ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type 0 to 70 UCC3800N & no Sb/Br) UCC3800PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR 0 to 70 3800 & no Sb/Br) UCC3801D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3801 & no Sb/Br) UCC3801DG4 ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3801 & no Sb/Br) UCC3801DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3801 & no Sb/Br) UCC3801N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type 0 to 70 UCC3801N & no Sb/Br) UCC3801NG4 ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type 0 to 70 UCC3801N & no Sb/Br) UCC3801PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR 0 to 70 3801 & no Sb/Br) UCC3801PWTR ACTIVE TSSOP PW 8 2000 Green (RoHS NIPDAU Level-2-260C-1 YEAR 0 to 70 3801 & no Sb/Br) UCC3802D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3802 & no Sb/Br) UCC3802DG4 ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3802 & no Sb/Br) Addendum-Page 4

PACKAGE OPTION ADDENDUM www.ti.com 12-May-2020 Orderable Device Status Package Type Package Pins Package Eco Plan Lead/Ball Finish MSL Peak Temp Op Temp (°C) Device Marking Samples (1) Drawing Qty (2) (6) (3) (4/5) UCC3802DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3802 & no Sb/Br) UCC3802DTRG4 ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3802 & no Sb/Br) UCC3802N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type 0 to 70 UCC3802N & no Sb/Br) UCC3802PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR 0 to 70 3802 & no Sb/Br) UCC3803D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3803 & no Sb/Br) UCC3803DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3803 & no Sb/Br) UCC3803DTRG4 ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3803 & no Sb/Br) UCC3803N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type 0 to 70 UCC3803N & no Sb/Br) UCC3803PWTR ACTIVE TSSOP PW 8 2000 Green (RoHS NIPDAU Level-2-260C-1 YEAR 0 to 70 3803 & no Sb/Br) UCC3803PWTRG4 ACTIVE TSSOP PW 8 2000 Green (RoHS NIPDAU Level-2-260C-1 YEAR 0 to 70 3803 & no Sb/Br) UCC3804D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3804 & no Sb/Br) UCC3804DG4 ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3804 & no Sb/Br) UCC3804DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3804 & no Sb/Br) UCC3804DTRG4 ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3804 & no Sb/Br) UCC3804N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type 0 to 70 UCC3804N & no Sb/Br) UCC3804NG4 ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type 0 to 70 UCC3804N & no Sb/Br) UCC3804PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR 0 to 70 3804 & no Sb/Br) UCC3804PWTR ACTIVE TSSOP PW 8 2000 Green (RoHS NIPDAU Level-2-260C-1 YEAR 0 to 70 3804 & no Sb/Br) Addendum-Page 5

PACKAGE OPTION ADDENDUM www.ti.com 12-May-2020 Orderable Device Status Package Type Package Pins Package Eco Plan Lead/Ball Finish MSL Peak Temp Op Temp (°C) Device Marking Samples (1) Drawing Qty (2) (6) (3) (4/5) UCC3805D ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3805 & no Sb/Br) UCC3805DG4 ACTIVE SOIC D 8 75 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3805 & no Sb/Br) UCC3805DTR ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3805 & no Sb/Br) UCC3805DTRG4 ACTIVE SOIC D 8 2500 Green (RoHS NIPDAU Level-1-260C-UNLIM 0 to 70 UCC3805 & no Sb/Br) UCC3805N ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type 0 to 70 UCC3805N & no Sb/Br) UCC3805NG4 ACTIVE PDIP P 8 50 Green (RoHS NIPDAU N / A for Pkg Type 0 to 70 UCC3805N & no Sb/Br) UCC3805PW ACTIVE TSSOP PW 8 150 Green (RoHS NIPDAU Level-2-260C-1 YEAR 0 to 70 3805 & no Sb/Br) (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may reference these types of products as "Pb-Free". RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption. Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based flame retardants must also meet the <=1000ppm threshold requirement. (3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. (4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device. (5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation of the previous line and the two combined represent the entire Device Marking for that device. Addendum-Page 6

PACKAGE OPTION ADDENDUM www.ti.com 12-May-2020 (6) Lead/Ball Finish - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead/Ball Finish values may wrap to two lines if the finish value exceeds the maximum column width. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release. In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis. OTHER QUALIFIED VERSIONS OF UCC1800, UCC1801, UCC1802, UCC1803, UCC1804, UCC1805, UCC2800, UCC2801, UCC2802, UCC2802M, UCC2803, UCC2804, UCC2805, UCC3800, UCC3801, UCC3802, UCC3803, UCC3804, UCC3805 : •Catalog: UCC3800, UCC3801, UCC3802, UCC3803, UCC3804, UCC3805, UCC2802 •Automotive: UCC2800-Q1, UCC2801-Q1, UCC2802-Q1, UCC2802-Q1, UCC2803-Q1, UCC2804-Q1, UCC2805-Q1 •Enhanced Product: UCC2800-EP, UCC2801-EP, UCC2802-EP, UCC2802-EP, UCC2803-EP, UCC2804-EP, UCC2805-EP •Military: UCC2802M, UCC1800, UCC1801, UCC1802, UCC1803, UCC1804, UCC1805 NOTE: Qualified Version Definitions: •Catalog - TI's standard catalog product •Automotive - Q100 devices qualified for high-reliability automotive applications targeting zero defects •Enhanced Product - Supports Defense, Aerospace and Medical Applications •Military - QML certified for Military and Defense Applications Addendum-Page 7

PACKAGE MATERIALS INFORMATION www.ti.com 12-May-2020 TAPE AND REEL INFORMATION *Alldimensionsarenominal Device Package Package Pins SPQ Reel Reel A0 B0 K0 P1 W Pin1 Type Drawing Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant (mm) W1(mm) UCC2800DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC2801DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC2802DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC2803DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC2803PWTR TSSOP PW 8 2000 330.0 12.4 7.0 3.6 1.6 8.0 12.0 Q1 UCC2804DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC2804PWTR TSSOP PW 8 2000 330.0 12.4 7.0 3.6 1.6 8.0 12.0 Q1 UCC2805DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC2805PWR TSSOP PW 8 2000 330.0 12.4 7.0 3.6 1.6 8.0 12.0 Q1 UCC3800DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC3801DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC3801PWTR TSSOP PW 8 2000 330.0 12.4 7.0 3.6 1.6 8.0 12.0 Q1 UCC3802DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC3803DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC3803PWTR TSSOP PW 8 2000 330.0 12.4 7.0 3.6 1.6 8.0 12.0 Q1 UCC3804DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 UCC3804PWTR TSSOP PW 8 2000 330.0 12.4 7.0 3.6 1.6 8.0 12.0 Q1 UCC3805DTR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 PackMaterials-Page1

PACKAGE MATERIALS INFORMATION www.ti.com 12-May-2020 *Alldimensionsarenominal Device PackageType PackageDrawing Pins SPQ Length(mm) Width(mm) Height(mm) UCC2800DTR SOIC D 8 2500 340.5 338.1 20.6 UCC2801DTR SOIC D 8 2500 340.5 338.1 20.6 UCC2802DTR SOIC D 8 2500 340.5 338.1 20.6 UCC2803DTR SOIC D 8 2500 340.5 338.1 20.6 UCC2803PWTR TSSOP PW 8 2000 367.0 367.0 35.0 UCC2804DTR SOIC D 8 2500 340.5 338.1 20.6 UCC2804PWTR TSSOP PW 8 2000 367.0 367.0 35.0 UCC2805DTR SOIC D 8 2500 340.5 338.1 20.6 UCC2805PWR TSSOP PW 8 2000 367.0 367.0 35.0 UCC3800DTR SOIC D 8 2500 340.5 338.1 20.6 UCC3801DTR SOIC D 8 2500 340.5 338.1 20.6 UCC3801PWTR TSSOP PW 8 2000 367.0 367.0 35.0 UCC3802DTR SOIC D 8 2500 340.5 338.1 20.6 UCC3803DTR SOIC D 8 2500 340.5 338.1 20.6 UCC3803PWTR TSSOP PW 8 2000 367.0 367.0 35.0 UCC3804DTR SOIC D 8 2500 340.5 338.1 20.6 UCC3804PWTR TSSOP PW 8 2000 367.0 367.0 35.0 UCC3805DTR SOIC D 8 2500 340.5 338.1 20.6 PackMaterials-Page2

None

PACKAGE OUTLINE D0008A SOIC - 1.75 mm max height SCALE 2.800 SMALL OUTLINE INTEGRATED CIRCUIT C SEATING PLANE .228-.244 TYP [5.80-6.19] .004 [0.1] C A PIN 1 ID AREA 6X .050 [1.27] 8 1 2X .189-.197 [4.81-5.00] .150 NOTE 3 [3.81] 4X (0 -15 ) 4 5 8X .012-.020 B .150-.157 [0.31-0.51] .069 MAX [3.81-3.98] .010 [0.25] C A B [1.75] NOTE 4 .005-.010 TYP [0.13-0.25] 4X (0 -15 ) SEE DETAIL A .010 [0.25] .004-.010 0 - 8 [0.11-0.25] .016-.050 [0.41-1.27] DETAIL A (.041) TYPICAL [1.04] 4214825/C 02/2019 NOTES: 1. Linear dimensions are in inches [millimeters]. Dimensions in parenthesis are for reference only. Controlling dimensions are in inches. Dimensioning and tolerancing per ASME Y14.5M. 2. This drawing is subject to change without notice. 3. This dimension does not include mold flash, protrusions, or gate burrs. Mold flash, protrusions, or gate burrs shall not exceed .006 [0.15] per side. 4. This dimension does not include interlead flash. 5. Reference JEDEC registration MS-012, variation AA. www.ti.com

EXAMPLE BOARD LAYOUT D0008A SOIC - 1.75 mm max height SMALL OUTLINE INTEGRATED CIRCUIT 8X (.061 ) [1.55] SYMM SEE DETAILS 1 8 8X (.024) [0.6] SYMM (R.002 ) TYP [0.05] 5 4 6X (.050 ) [1.27] (.213) [5.4] LAND PATTERN EXAMPLE EXPOSED METAL SHOWN SCALE:8X SOLDER MASK SOLDER MASK METAL OPENING OPENING METAL UNDER SOLDER MASK EXPOSED METAL EXPOSED METAL .0028 MAX .0028 MIN [0.07] [0.07] ALL AROUND ALL AROUND NON SOLDER MASK SOLDER MASK DEFINED DEFINED SOLDER MASK DETAILS 4214825/C 02/2019 NOTES: (continued) 6. Publication IPC-7351 may have alternate designs. 7. Solder mask tolerances between and around signal pads can vary based on board fabrication site. www.ti.com

EXAMPLE STENCIL DESIGN D0008A SOIC - 1.75 mm max height SMALL OUTLINE INTEGRATED CIRCUIT 8X (.061 ) [1.55] SYMM 1 8 8X (.024) [0.6] SYMM (R.002 ) TYP [0.05] 5 4 6X (.050 ) [1.27] (.213) [5.4] SOLDER PASTE EXAMPLE BASED ON .005 INCH [0.125 MM] THICK STENCIL SCALE:8X 4214825/C 02/2019 NOTES: (continued) 8. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate design recommendations. 9. Board assembly site may have different recommendations for stencil design. www.ti.com

MECHANICAL DATA MCER001A – JANUARY 1995 – REVISED JANUARY 1997 JG (R-GDIP-T8) CERAMIC DUAL-IN-LINE 0.400 (10,16) 0.355 (9,00) 8 5 0.280 (7,11) 0.245 (6,22) 1 4 0.065 (1,65) 0.045 (1,14) 0.063 (1,60) 0.020 (0,51) MIN 0.310 (7,87) 0.015 (0,38) 0.290 (7,37) 0.200 (5,08) MAX Seating Plane 0.130 (3,30) MIN 0.023 (0,58) 0°–15° 0.015 (0,38) 0.100 (2,54) 0.014 (0,36) 0.008 (0,20) 4040107/C 08/96 NOTES: A. All linear dimensions are in inches (millimeters). B. This drawing is subject to change without notice. C. This package can be hermetically sealed with a ceramic lid using glass frit. D. Index point is provided on cap for terminal identification. E. Falls within MIL STD 1835 GDIP1-T8 • POST OFFICE BOX 655303 DALLAS, TEXAS 75265

None

PACKAGE OUTLINE PW0008A TSSOP - 1.2 mm max height SCALE 2.800 SMALL OUTLINE PACKAGE C 6.6 TYP SEATING PLANE 6.2 PIN 1 ID A 0.1 C AREA 6X 0.65 8 1 3.1 2X 2.9 NOTE 3 1.95 4 5 0.30 8X 0.19 4.5 1.2 MAX B 0.1 C A B 4.3 NOTE 4 (0.15) TYP SEE DETAIL A 0.25 GAGE PLANE 0.15 0.75 0 - 8 0.05 0.50 DETAIL A TYPICAL 4221848/A 02/2015 NOTES: 1. All linear dimensions are in millimeters. Any dimensions in parenthesis are for reference only. Dimensioning and tolerancing per ASME Y14.5M. 2. This drawing is subject to change without notice. 3. This dimension does not include mold flash, protrusions, or gate burrs. Mold flash, protrusions, or gate burrs shall not exceed 0.15 mm per side. 4. This dimension does not include interlead flash. Interlead flash shall not exceed 0.25 mm per side. 5. Reference JEDEC registration MO-153, variation AA. www.ti.com

EXAMPLE BOARD LAYOUT PW0008A TSSOP - 1.2 mm max height SMALL OUTLINE PACKAGE 8X (1.5) 8X (0.45) SYMM (R0.05) 1 TYP 8 SYMM 6X (0.65) 5 4 (5.8) LAND PATTERN EXAMPLE SCALE:10X SOOPLEDNEINRG MASK METAL MSOELTDAEL RU NMDAESRK SOOPLEDNEINRG MASK 0.05 MAX 0.05 MIN ALL AROUND ALL AROUND NON SOLDER MASK SOLDER MASK DEFINED DEFINED SOLDER MASK DETAILS NOT TO SCALE 4221848/A 02/2015 NOTES: (continued) 6. Publication IPC-7351 may have alternate designs. 7. Solder mask tolerances between and around signal pads can vary based on board fabrication site. www.ti.com

EXAMPLE STENCIL DESIGN PW0008A TSSOP - 1.2 mm max height SMALL OUTLINE PACKAGE 8X (1.5) SYMM (R0.05) TYP 8X (0.45) 1 8 SYMM 6X (0.65) 5 4 (5.8) SOLDER PASTE EXAMPLE BASED ON 0.125 mm THICK STENCIL SCALE:10X 4221848/A 02/2015 NOTES: (continued) 8. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate design recommendations. 9. Board assembly site may have different recommendations for stencil design. www.ti.com

IMPORTANTNOTICEANDDISCLAIMER TI PROVIDES TECHNICAL AND RELIABILITY DATA (INCLUDING DATASHEETS), DESIGN RESOURCES (INCLUDING REFERENCE DESIGNS), APPLICATION OR OTHER DESIGN ADVICE, WEB TOOLS, SAFETY INFORMATION, AND OTHER RESOURCES “AS IS” AND WITH ALL FAULTS, AND DISCLAIMS ALL WARRANTIES, EXPRESS AND IMPLIED, INCLUDING WITHOUT LIMITATION ANY IMPLIED WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE OR NON-INFRINGEMENT OF THIRD PARTY INTELLECTUAL PROPERTY RIGHTS. These resources are intended for skilled developers designing with TI products. You are solely responsible for (1) selecting the appropriate TI products for your application, (2) designing, validating and testing your application, and (3) ensuring your application meets applicable standards, and any other safety, security, or other requirements. These resources are subject to change without notice. TI grants you permission to use these resources only for development of an application that uses the TI products described in the resource. Other reproduction and display of these resources is prohibited. No license is granted to any other TI intellectual property right or to any third party intellectual property right. TI disclaims responsibility for, and you will fully indemnify TI and its representatives against, any claims, damages, costs, losses, and liabilities arising out of your use of these resources. TI’s products are provided subject to TI’s Terms of Sale (www.ti.com/legal/termsofsale.html) or other applicable terms available either on ti.com or provided in conjunction with such TI products. TI’s provision of these resources does not expand or otherwise alter TI’s applicable warranties or warranty disclaimers for TI products. Mailing Address: Texas Instruments, Post Office Box 655303, Dallas, Texas 75265 Copyright © 2020, Texas Instruments Incorporated