LT1930/LT1930A 1A, 1.2MHz/2.2MHz, Step-Up DC/DC Converters in ThinSOT FEATURES DESCRIPTIOU n 1.2MHz Switching Frequency (LT1930) The LT®1930 and LT1930A are the industry’s highest n 2.2MHz Switching Frequency (LT1930A) power SOT-23 switching regulators. Both include an n Low V Switch: 400mV at 1A internal 1A, 36V switch allowing high current outputs to be CESAT n High Output Voltage: Up to 34V generated in a small footprint. The LT1930 switches at n 5V at 480mA from 3.3V Input (LT1930) 1.2MHz, allowing the use of tiny, low cost and low height n 12V at 250mA from 5V Input (LT1930A) capacitors and inductors. The faster LT1930A switches at n Wide Input Range: 2.6V to 16V 2.2MHz, enabling further reductions in inductor size. n Uses Small Surface Mount Components Complete regulator solutions approaching one tenth of a n Low Shutdown Current: <1m A square inch in area are achievable with these devices. n Low Profile (1mm) ThinSOTTM Package Multiple output power supplies can now use a separate n Pin-for-Pin Compatible with the LT1613 regulator for each output voltage, replacing cumbersome quasi-regulated approaches using a single regulator and APPLICATIOU S custom transformers. A constant frequency internally compensated current mode n TFT-LCD Bias Supply PWM architecture results in low, predictable output noise n Digital Cameras that is easy to filter. Low ESR ceramic capacitors can be n Cordless Phones used at the output, further reducing noise to the millivolt n Battery Backup level. The high voltage switch on the LT1930/LT1930A is n Medical Diagnostic Equipment rated at 36V, making the device ideal for boost converters n Local 5V or 12V Supply up to 34V as well as for single-ended primary inductance n External Modems converter (SEPIC) and flyback designs. The LT1930 can n PC Cards generate 5V at up to 480mA from a 3.3V supply or 5V at n xDSL Power Supply 300mA from four alkaline cells in a SEPIC design. , LTC and LT are registered trademarks of Linear Technology Corporation The LT1930/LT1930A are available in the 5-lead ThinSOT ThinSOT is a trademark of Linear Technology Corporation. package. TYPICAL APPLICATIOU Efficiency L1 90 V5IVN 10µH D1 V12OVUT 85 VIN = 5V 5 1 R1 300mA VIN = 3.3V SC2H.12DµNF 4 SVHIDNNLT1930SWFB 3 113k C103p*F C4.27µF NCY (%) 778050 E CI GND R2 FFI 65 13.3k E 2 60 C1: TAIYO-YUDEN X5R LMK212BJ225MG C2: TAIYO-YUDEN X5R EMK316BJ475ML 1930/A F01 55 D1: ON SEMICONDUCTOR MBR0520 L1: SUMIDA CR43-100 50 *OPTIONAL 0 100 200 300 400 LOAD CURRENT (mA) Figure 1. 5V to 12V, 300mA Step-Up DC/DC Converter 1930 TA01 1

LT1930/LT1930A ABSOLUTE W AXIW UW RATIU GS PACKAGE/ORDER IU FORW ATIOU (Note 1) ORDER PART V Voltage .............................................................. 16V NUMBER IN SW Voltage................................................–0.4V to 36V TOP VIEW LT1930ES5 FB Voltage .............................................................. 2.5V SW 1 5 VIN LT1930AES5 Current Into FB Pin.............................................. – 1mA GND 2 SHDN Voltage......................................................... 10V FB 3 4 SHDN S5 PART MARKING Maximum Junction Temperature......................... 125(cid:176) C S5 PACKAGE Operating Temperature Range (Note 2).. –40(cid:176) C to 85(cid:176) C 5-LEAD PLASTIC SOT-23 LTKS Storage Temperature Range................. –65(cid:176) C to 150(cid:176) C TJMAX = 125(cid:176)C, q JA = 256(cid:176)C/W LTSQ Lead Temperature (Soldering, 10 sec)..................300(cid:176) C Consult LTC Marketing for parts specified with wider operating temperature ranges. ELECTRICAL CHARACTERISTICS The l denotes specifications which apply over the full operating temperature range, otherwise specifications are T = 25(cid:176) C. A V = 3V, V = V unless otherwise noted. (Note 2) IN SHDN IN LT1930 LT1930A PARAMETER CONDITIONS MIN TYP MAX MIN TYP MAX UNITS Minimum Operating Voltage 2.45 2.6 2.45 2.6 V Maximum Operating Voltage 16 16 V Feedback Voltage 1.240 1.255 1.270 1.240 1.255 1.270 V l 1.230 1.280 1.230 1.280 V FB Pin Bias Current V = 1.255V l 120 360 240 720 nA FB Quiescent Current V = 2.4V, Not Switching 4.2 6 5.5 8 mA SHDN Quiescent Current in Shutdown V = 0V, V = 3V 0.01 1 0.01 1 m A SHDN IN Reference Line Regulation 2.6V £ V £ 16V 0.01 0.05 0.01 0.05 %/V IN Switching Frequency 1 1.2 1.4 1.8 2.2 2.6 MHz l 0.85 1.6 1.6 2.9 MHz Maximum Duty Cycle l 84 90 75 90 % Switch Current Limit (Note 3) 1 1.2 2 1 1.2 2.5 A Switch V I = 1A 400 600 400 600 mV CESAT SW Switch Leakage Current V = 5V 0.01 1 0.01 1 m A SW SHDN Input Voltage High 2.4 2.4 V SHDN Input Voltage Low 0.5 0.5 V SHDN Pin Bias Current V = 3V 16 32 35 70 m A SHDN V = 0V 0 0.1 0 0.1 m A SHDN Note 1: Absolute Maximum Ratings are those values beyond which the life operating temperature range are assured by design, characterization and of a device may be impaired. correlation with statistical process controls. Note 2: The LT1930E/LT1930AE are guaranteed to meet performance Note 3: Current limit guaranteed by design and/or correlation to static test. specifications from 0(cid:176) C to 70(cid:176) C. Specifications over the –40(cid:176) C to 85(cid:176) C 2

LT1930/LT1930A TYPICAL PERFORW AU CE CHARACTERISTICS Quiescent Current FB Pin Voltage SHDN Pin Current 7.0 1.28 90 NOT SWITCHING 6.5 80 1.27 LT1930A 70 QUIESCENT CURRENT (mA) 65544.....05050 LT1930LT1930A FB VOLTAGE (V)111...222456 µSHDN PIN CURRENT (A) 312564000000 LT1930 1.23 3.5 0 3.0 1.22 –10 –50 –25 0 25 50 75 100 –50 –25 0 25 50 75 100 0 1 2 3 4 5 6 TEMPERATURE (°C) TEMPERATURE (°C) SHDN PIN VOLTAGE (V) 1930/A G01 1930/A G02 1930/A G03 Current Limit Switch Saturation Voltage Oscillator Frequency 1.6 0.45 2.5 1.4 0.40 2.3 0.35 2.1 LT1930A 1.2 URRENT LI MIT (A) 001...860 V (V)CESAT0000....22310505 REQUENCY (MHz) 1111....9753 LT1930 C F 1.1 0.4 0.10 0.9 0.2 0.05 0.7 0 0 0.5 10 20 30 40 50 60 70 80 90 0 0.2 0.4 0.6 0.8 1.0 1.2 –50 –25 0 25 50 75 100 DUTY CYCLE (%) SWITCH CURRENT (A) TEMPERATURE (°C) 1930/A G04 1930/A G05 1930/A G06 PIU FUU CTIOU S SW (Pin 1): Switch Pin. Connect inductor/diode here. SHDN (Pin 4): Shutdown Pin. Tie to 2.4V or more to enable Minimize trace area at this pin to reduce EMI. device. Ground to shut down. GND (Pin 2): Ground. Tie directly to local ground plane. V (Pin 5): Input Supply Pin. Must be locally bypassed. IN FB (Pin 3): Feedback Pin. Reference voltage is 1.255V. Connect resistive divider tap here. Minimize trace area at FB. Set V according to V = 1.255V(1 + R1/R2). OUT OUT 3

LT1930/LT1930A BLOCK DIAGRAW VIN 5 RE1F.E2R5E5NVCE + COMPARATOR 1 SW A1 – DRIVER – RC A2 R S Q Q1 VOUT CC + + R1 (EXTERNAL) FB S 0.01W R2 (EXTERNAL) – RAMP GENERATOR SHUTDOWN 4 SHDN 3 FB 2 GND 1.2MHz 1930/A BD OSCILLATOR* *2.2MHz FOR LT1930A Figure 2. Block Diagram OPERATIOU The LT1930 uses a constant frequency, current-mode this manner, the error amplifier sets the correct peak control scheme to provide excellent line and load regula- current level to keep the output in regulation. If the error tion. Operation can be best understood by referring to the amplifier’s output increases, more current is delivered to block diagram in Figure 2. At the start of each oscillator the output; if it decreases, less current is delivered. The cycle, the SR latch is set, which turns on the power switch LT1930 has a current limit circuit not shown in Figure 2. Q1. A voltage proportional to the switch current is added The switch current is constantly monitored and not al- to a stabilizing ramp and the resulting sum is fed into the lowed to exceed the maximum switch current (typically positive terminal of the PWM comparator A2. When this 1.2A). If the switch current reaches this value, the SR latch voltage exceeds the level at the negative input of A2, the SR is reset regardless of the state of comparator A2. This latch is reset turning off the power switch. The level at the current limit helps protect the power switch as well as the negative input of A2 is set by the error amplifier A1, and is external components connected to the LT1930. simply an amplified version of the difference between the The block diagram for the LT1930A (not shown) is iden- feedback voltage and the reference voltage of 1.255V. In tical except that the oscillator frequency is 2.2MHz. 4

LT1930/LT1930A APPLICATIOUNS INUFORWMATIOUN LT1930 AND LT1930A DIFFERENCES iron types. Choose an inductor that can handle at least 1A without saturating, and ensure that the inductor has a low Switching Frequency DCR (copper-wire resistance) to minimize I2R power losses. A 4.7m H or 10m H inductor will be the best choice for most The key difference between the LT1930 and LT1930A is LT1930 designs. For LT1930A designs, a 2.2m H to 4.7m H the faster switching frequency of the LT1930A. At 2.2MHz, inductor will usually suffice. Note that in some applica- the LT1930A switches at nearly twice the rate of the tions, the current handling requirements of the inductor LT1930. Care must be taken in deciding which part to use. can be lower, such as in the SEPIC topology where each The high switching frequency of the LT1930A allows inductor only carries one-half of the total switch current. smaller cheaper inductors and capacitors to be used in a given application, but with a slight decrease in efficiency Table 1. Recommended Inductors – LT1930 and maximum output current when compared to the MAX SIZE LT1930. Generally, if efficiency and maximum output L DCR L · W · H current are critical, the LT1930 should be used. If applica- PART (m H) mW (mm) VENDOR tion size and cost are more important, the LT1930A will be CDRH5D18-4R1 4.1 57 4.5 · 4.7 · 2.0 Sumida the better choice. In many applications, tiny inexpensive CDRH5D18-100 10 124 (847) 956-0666 CR43-4R7 4.7 109 3.2 · 2.5 · 2.0 www.sumida.com chip inductors can be used with the LT1930A, reducing CR43-100 10 182 solution cost. DS1608-472 4.7 60 4.5 · 6.6 · 2.9 Coilcraft DS1608-103 10 75 (847) 639-6400 Duty Cycle www.coilcraft.com The maximum duty cycle (DC) of the LT1930A is 75% ELT5KT4R7M 4.7 240 5.2 · 5.2 · 1.1 Panasonic ELT5KT6R8M 6.8 360 (408) 945-5660 compared to 84% for the LT1930. The duty cycle for a www.panasonic.com given application using the boost topology is given by: Table 2. Recommended Inductors – LT1930A |V |–|V | DC = OUT IN MAX SIZE |V | L DCR L · W · H OUT PART (m H) mW (mm) VENDOR For a 5V to 12V application, the DC is 58.3% indicating that LQH3C2R2M24 2.2 126 3.2 · 2.5 · 2.0 Murata the LT1930A could be used. A 5V to 24V application has LQH3C4R7M24 4.7 195 (404) 573-4150 a DC of 79.2% making the LT1930 the right choice. The www.murata.com LT1930A can still be used in applications where the DC, as CR43-2R2 2.2 71 4.5 · 4.0 · 3.0 Sumida CR43-3R3 3.3 86 (847) 956-0666 calculated above, is above 75%. However, the part must www.sumida.com be operated in the discontinuous conduction mode so that 1008PS-272 2.7 100 3.7 · 3.7 · 2.6 Coilcraft the actual duty cycle is reduced. 1008PS-332 3.3 110 (800) 322-2645 www.coilcraft.com ELT5KT3R3M 3.3 204 5.2 · 5.2 · 1.1 Panasonic INDUCTOR SELECTION (408) 945-5660 Several inductors that work well with the LT1930 are listed www.panasonic.com in Table 1 and those for the LT1930A are listed in Table 2. The inductors shown in Table 2 for use with the LT1930A These tables are not complete, and there are many other were chosen for small size. For better efficiency, use manufacturers and devices that can be used. Consult each similar valued inductors with a larger volume. For manufacturer for more detailed information and for their example, the Sumida CR43 series in values ranging from entire selection of related parts, as many different sizes and 2.2m H to 4.7m H will give an LT1930A application a few shapes are available. Ferrite core inductors should be used percentage points increase in efficiency, compared to the to obtain the best efficiency, as core losses at 1.2MHz are smaller Murata LQH3C Series. much lower for ferrite cores than for cheaper powdered- 5

LT1930/LT1930A APPLICATIOUNS INUFORWMATIOUN CAPACITOR SELECTION By choosing the appropriate values for the resistor and capacitor, the zero frequency can be designed to improve Low ESR (equivalent series resistance) capacitors should the phase margin of the overall converter. The typical be used at the output to minimize the output ripple voltage. target value for the zero frequency is between 35kHz to Multi-layer ceramic capacitors are an excellent choice, as 55kHz. Figure 3 shows the transient response of the step- they have extremely low ESR and are available in very up converter from Figure 1 without the phase lead capaci- small packages. X5R dielectrics are preferred, followed by tor C3. The phase margin is reduced as evidenced by more X7R, as these materials retain the capacitance over wide ringing in both the output voltage and inductor current. A voltage and temperature ranges. A 4.7m F to 10m F output 10pF capacitor for C3 results in better phase margin, capacitor is sufficient for most applications, but systems which is revealed in Figure 4 as a more damped response with very low output currents may need only a 1m F or 2.2m F and less overshoot. Figure 5 shows the transient response output capacitor. Solid tantalum or OSCON capacitors can when a 33m F tantalum capacitor with no phase lead be used, but they will occupy more board area than a capacitor is used on the output. The higher output voltage ceramic and will have a higher ESR. Always use a capacitor ripple is revealed in the upper waveform as a set of double with a sufficient voltage rating. lines. The transient response is not greatly improved Ceramic capacitors also make a good choice for the input which implies that the ESR zero frequency is too high to decoupling capacitor, which should be placed as close as increase the phase margin. possible to the LT1930/LT1930A. A 1m F to 4.7m F input capacitor is sufficient for most applications. Table 3 shows a list of several ceramic capacitor manufacturers. Consult VOUT 0.2V/DIV the manufacturers for detailed information on their entire AC COUPLED selection of ceramic parts. ILI 0.5A/DIV Table 3. Ceramic Capacitor Manufacturers AC COUPLED Taiyo Yuden (408) 573-4150 www.t-yuden.com LOAD250mA AVX (803) 448-9411 www.avxcorp.com CURRENT150mA Murata (714) 852-2001 www.murata.com 50m s/DIV 1930 F03 Figure 3. Transient Response of Figure 1's Step-Up The decision to use either low ESR (ceramic) capacitors or Converter without Phase Lead Capacitor the higher ESR (tantalum or OSCON) capacitors can affect the stability of the overall system. The ESR of any capaci- tor, along with the capacitance itself, contributes a zero to VOUT 0.2V/DIV the system. For the tantalum and OSCON capacitors, this AC COUPLED zero is located at a lower frequency due to the higher value ILI of the ESR, while the zero of a ceramic capacitor is at a 0.5A/DIV AC COUPLED much higher frequency and can generally be ignored. A phase lead zero can be intentionally introduced by LOAD250mA CURRENT 150mA placing a capacitor (C3) in parallel with the resistor (R1) 50m s/DIV 1930 F04 between V and V as shown in Figure 1. The frequency OUT FB Figure 4. Transient Response of Figure 1's Step-Up of the zero is determined by the following equation. Converter with 10pF Phase Lead Capacitor 1 ƒ = Z 2p •R1•C3 6

LT1930/LT1930A APPLICATIOUNS INUFORWMATIOUN LAYOUT HINTS VOUT 0.2V/DIV The high speed operation of the LT1930/LT1930A AC COUPLED demands careful attention to board layout. You will not get ILI advertised performance with careless layout. Figure 6 0.5A/DIV shows the recommended component placement. AC COUPLED LOAD250mA CURRENT150mA 200m s/DIV 1930 F04 Figure 5. Transient Response of Step-Up Converter with 33m F L1 Tantalum Output Capacitor and No Phase Lead Capacitor D1 C1 + VOUT VIN DIODE SELECTION + C2 A Schottky diode is recommended for use with the LT1930/ SHUTDOWN R2 LT1930A. The Motorola MBR0520 is a very good choice. Where the switch voltage exceeds 20V, use the MBR0530 R1 C3 GND (a 30V diode). Where the switch voltage exceeds 30V, use 1930 F06 the MBR0540 (a 40V diode). These diodes are rated to Figure 6. Suggested Layout handle an average forward current of 0.5A. In applications where the average forward current of the diode exceeds 0.5A, a Microsemi UPS5817 rated at 1A is recommended. Driving SHDN Above 10V The maximum voltage allowed on the SHDN pin is 10V. If SETTING OUTPUT VOLTAGE you wish to use a higher voltage, you must place a resistor in series with SHDN. A good value is 121k. Figure 7 shows To set the output voltage, select the values of R1 and R2 a circuit where V = 16V and SHDN is obtained from V . (see Figure 1) according to the following equation. IN IN The voltage on the SHDN pin is kept below 10V. (cid:230) (cid:246) V R1=R2(cid:231) OUT –1(cid:247) Ł 1.255V ł A good value for R2 is 13.3k which sets the current in the resistor divider chain to 1.255V/13.3k = 94.7m A. D1 L1 1V6IVN VOUT 5 1 C1 121k VIN SW R1 LT1930 4 3 C2 SHDN FB GND R2 2 1930 F07 Figure 7. Keeping SHDN Below 10V 7

LT1930/LT1930A TYPICAL APPLICATIOU S Efficiency 4-Cell to 5V SEPIC Converter 80 C3 VIN = 6.5V 4V TO 6.5V 10Lµ1H 1µF D1 VOUT 75 VIN = 4V 5V 70 5 1 300mA %) 65 C2.12µF VIN SW CY ( BA4T-TCEERLYL SHDN 4 SHDNLT1930 FB 3 243k L120µH C102µF EFFICIEN 6505 GND 82.5k 50 2 45 C1: TAIYO-YUDEN X5R LMK212BJ225MG 1930 TA02a C2: TAIYO-YUDEN X5R JMK316BJ106ML D1: ON SEMICONDUCTOR MBR0520 40 0 100 200 300 400 500 C3: TAIYO-YUDEN X5R LMK212BJ105MG L1, L2: MURATA LQH3C100K24 LOAD CURRENT (mA) 1930 TA02b 4-Cell to 5V SEPIC Converter with Coupled Inductors 5V to 24V Boost Converter C3 4V TO 6.5V 1L01µAH • 1µF D1 V5VOUT VIN 10Lµ1H D1 V24OVUT 5V 5 1 300mA 5 1 90mA C1 VIN SW C1 VIN SW R1 4-CELL 2.2µF LT1930 243k • 4.7µF LT1930 665k C2 BATTERY SHDN 4 SHDN FB 3 L110µBH C102µF SHDN 4 SHDN FB 3 2.2µF GND 82.5k GND R2 2 2 36.5k C1: TAIYO-YUDEN X5R LMK212BJ225MG C1: TAIYO-YUDEN X5R EMK316BJ475ML C2: TAIYO-YUDEN X5R JMK316BJ106ML 1930/A TA03 C2: TAIYO-YUDEN X5R JMK212BJ475MG 1930/A TA04 C3: TAIYO-YUDEN X5R LMK212BJ105MG D1: ON SEMICONDUCTOR MBR0530 D1: ON SEMICONDUCTOR MBR0520 L1: SUMIDA CR43-100 L1: SUMIDA CLS62-100 – 15V Dual Output Converter with Output Disconnect C4 3.L31µH 1µF D1 VIN 15V 5V 70mA 5 1 C1 VIN SW C5 R1 2.2µF 1µF 147k LT1930 D2 C2 4 3 2.2µF OFF ON SHDN FB GND R2 13.3k 2 C1: TAIYO-YUDEN X5R LMK212BJ225MG C6 C2, C3: TAIYO-YUDEN X5R EMK316BJ225ML D3 D4 2.2µF C4, C5: TAIYO-YUDEN X5R TMK316BJ105ML –15V (408) 573-4150 1930/A TA05 70mA D1 TO D4: ON SEMICONDUCTOR MBR0520 (800) 282-9855 L1: SUMIDA CR43-3R3 (874) 956-0666 8

LT1930/LT1930A TYPICAL APPLICATIOU S Boost Converter with Reverse Battery Protection L1 VIN M1 4.7µH D1 VOUT 3V to 6V 8V C1 5 1 C3 520mA AT VIN = 6V 2.2µF VIN SW R1 47pF 240mA AT VIN = 3V 60.4k LT1930 4 3 C2 SHDN SHDN FB 22µF GND R2 11.3k 2 C1: TAIYO-YUDEN X5R LMK432BJ226MM C2: TAIYO-YUDEN X5R LMK212BJ225MG 1930/A TA06 D1: ON SEMICONDUCTOR MBR0520 L1: SUMIDA CR43-4R7 M1: SILICONIX Si6433DQ 3.3V to 5V Boost Converter Efficiency L1 90 VIN 5.6µH D1 V5VOUT 85 VIN = 3.3V 3.3V 5 1 480mA 80 C1 VIN SW R1 VIN = 2.6V 4.7µF 40.2k %) 75 LT1930 C2 Y ( OFF ON 4 SHDN FB 3 10µF ENC 70 CI GND R2 FFI 65 13.3k E 2 60 C1: TAIYO-YUDEN X5R JMK212BJ475MG www.t-yuden.com C2: TAIYO-YUDEN X5R JMK316BJ106ML 1930/A TA07a 55 D1: ON SEMICONDUCTOR MBR0520 www.onsemi.com L1: SUMIDA CR43-5R6 www.sumida.com 50 0 100 200 300 400 500 LOAD CURRENT (mA) 1930/A TA07b 5V to 12V, 250mA Step-Up Converter Efficiency 90 VIN 2.L21µH D1 V12OVUT 85 VVIONU =T =5 V12V 5V 5 1 250mA 80 C2.12µF VINLT1930ASW R1115k C2 CY (%) 75 SHDN 4 SHDN FB 3 2.2µF CIEN 70 GND R2 EFFI 65 13.3k 2 60 C1: TAIYO-YUDEN X5R LMK212BJ225MG 55 C2: TAIYO-YUDEN X5R EMK316BJ225ML 1930/A TA08a D1: ON SEMICONDUCTOR MBR0520 50 L1: MURATA LQH3C2R2M24 0 50 100 150 200 250 300 LOAD CURRENT (mA) 1930/A TA08b 9

LT1930/LT1930A TYPICAL APPLICATIOU S 9V, 18V, –9V Triple Output TFT-LCD Bias Supply with Soft-Start D1 D2 18V 10mA C3 C4 0.1µF 1µF Start-Up Waveforms L1 4.7µH D5 VIN 9V 3.3V 200mA 9V OUTPUT 5 1 5V/DIV + R1 C1 VIN SW 124k 2.2µF RSS LT1930 30k 4 3 C5 –9V OUTPUT VSS SHDN FB 10µF 5V/DIV DSS 0V 3.3V 1N4148 CSS GND2 C0.21µF R202k 18V O1U0VT/PDUIVT 68nF C1: X5R OR X7R, 6.3V C2,C3, C5: X5R OR X7R, 10V D4 IL1 0.5A/DIV C4: X5R OR X7R, 25V 2ms/DIV D1- D4: BAT54S OR EQUIVALENT C6 D5: MBR0520 OR EQUIVALENT D3 1µF L1: PANASONIC ELT5KT4R7M –9V 10mA 1930/A TA11a 8V, 23V, –8V Triple Output TFT-LCD Bias Supply with Soft-Start D1 D2 D3 D4 23V 10mA C3 C4 C5 C6 0.1µF 0.1µF 0.1µF 1µF Start-Up Waveforms L1 4.7µH D7 VIN 8V 3.3V 220mA 8V OUTPUT 5 1 5V/DIV + R1 C1 VIN SW 113k 2.2µF R30SkS 4 LT1930 3 C7 –8V OUTPUT VSS SHDN FB 10µF 5V/DIV DSS 3.3V 1N4148 GND R2 0V 2 C2 21k 23V OUTPUT CSS 0.1µF 10V/DIV 68nF C1: X5R OR X7R, 6.3V C2-C4, C7, C8: X5R OR X7R, 10V D5 IL1 0.5A/DIV C5: X5R OR X7R, 16V C6: X5R OR X7R, 25V C8 2ms/DIV D1- D6: BAT54S OR EQUIVALENT D6 1µF D7: MBR0520 OR EQUIVALENT –8V L1: PANASONIC ELT5KT4R7M 10mA 1930/A TA12a 10

LT1930/LT1930A PACKAGE DESCRIPTIOU S5 Package 5-Lead Plastic SOT-23 (Reference LTC DWG # 05-08-1633) (Reference LTC DWG # 05-08-1635) 2.80 – 3.10 (.110 – .118) (NOTE 3) SOT-23 SOT-23 (Original) (ThinSOT) .90 – 1.45 1.00 MAX A (.035 – .057) (.039 MAX) A1 .00 – .15 .01 – .10 2.60 – 3.00 1.50 – 1.75 (.00 – .006) (.0004 – .004) (.102 – .118) (.059 – .069) .90 – 1.30 .80 – .90 (NOTE 3) A2 (.035 – .051) (.031 – .035) .35 – .55 .30 – .50 REF L (.014 – .021) (.012 – .019 REF) PIN ONE .95 .25 – .50 (.037) (.010 – .020) REF (5PLCS, NOTE 2) .20 (.008) A A2 DATUM ‘A’ L 1.90 .09 – .20 (.074) A1 NOTE: (.004 – .008) REF S5 SOT-23 0401 1. CONTROLLING DIMENSION: MILLIMETERS (NOTE 2) MILLIMETERS 2. DIMENSIONS ARE IN (INCHES) 3. DRAWING NOT TO SCALE 4. DIMENSIONS ARE INCLUSIVE OF PLATING 5. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 6. MOLD FLASH SHALL NOT EXCEED .254mm 7. PACKAGE EIAJ REFERENCE IS: SC-74A (EIAJ) FOR ORIGINAL JEDEL MO-193 FOR THIN Information furnished by Linear Technology Corporation is believed to be accurate and reliable. 11 However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen- tation that the interconnection of its circuits as described herein will not infringe on existing patent rights.

LT1930/LT1930A TYPICAL APPLICATIOU 3.3V to 5V, 450mA Step-Up Converter L1 VIN 2.2µH D1 V5VOUT 3.3V 5 1 450mA C1 VIN SW R1 2.2µF 30.1k LT1930A C2 4 3 10µF SHDN SHDN FB GND R2 10k 2 C1: TAIYO-YUDEN X5R LMK212BJ225MG C2: TAIYO-YUDEN X5R JMK316B106ML 1930/A TA09a D1: ON SEMICONDUCTOR MBR0520 L1: MURATA LQH3C2R2M24 Efficiency 90 3.3V to 5V Transient Response VIN = 3.3V 85 VOUT = 5V VOUT 80 50mV/DIV AC COUPLED %) 75 Y ( C AC C0O.U5AP/LDEIIDLVI FFICIEN 7605 E LOAD300mA 60 CURRENT200mA 55 20m s/DIV 1930 F03 50 0 100 200 300 400 500 LOAD CURRENT (mA) 1930/A TA09b RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LT1307 Single Cell Micropower 600kHz PWM DC/DC Converter 3.3V at 75mA from Single Cell, MSOP Package LT1316 Burst ModeTM Operation DC/DC Converter with Programmable Current Limit 1.5V Minimum, Precise Control of Peak Current Limit LT1317 2-Cell Micropower DC/DC Converter with Low-Battery Detector 3.3V at 200mA from 2 Cells, 600kHz Fixed Frequency LT1610 Single Cell Micropower DC/DC Converter 3V at 30mA from 1V, 1.7MHz Fixed Frequency LT1611 Inverting 1.4MHz Switching Regulator in 5-Lead ThinSOT –5V at 150mA from 5V Input, ThinSOT Package LT1613 1.4MHz Switching Regulator in 5-Lead ThinSOT 5V at 200mA from 3.3V Input, ThinSOT Package LT1615 Micropower Constant Off-Time DC/DC Converter in 5-Lead ThinSOT 20V at 12mA from 2.5V, ThinSOT Package LT1617 Micropower Inverting DC/DC Converter in 5-Lead ThinSOT –15V at 12mA from 2.5V Input, ThinSOT Package LT1931/LT1931A Inverting 1.2MHz/2.2MHz Switching Regulator in 5-Lead ThinSOT –5V at 350mA from 5V input, ThinSOT Package Burst Mode is a trademark of Linear Technology Corporation. 12 Linear Technology Corporation 1930af LT/TP 0801 2K • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 l FAX: (408) 434-0507 l www.linear.com ª LINEAR TECHNOLOGY CORPORATION 2001